A Novel Type High-Efficiency High-FrequencyLinked Full-Bridge DC-DC Converter Operating under Secondary-Side Series Resonant Principle for High-Power PV Generation Daisuke Tsukiyama, Yasuhiko Fukuda, and Shuji Miyake Dispersed Power System Division Daihen Corporation Osaka, Japan d-tsukiyama@daihen.co.jp (1) Saad Mekhilef, (2)Soon-Kurl Kwon, and (1), (2)Mutsuo Nakaoka (1) (2) University of Malaya, Malaysia Kyungnam University, Republic of Korea Abstract— This paper is mainly concerned with the development of a new state-of-the-art prototype, high-efficiency, phase-shift, soft-switching, pulse-modulated, full-bridge DC-DC power converter with a high-frequency power transformer, which is designed for utility-grid-tied photovoltaic (PV) power inverters. The proposed high-frequency transformer (HFTR) link DC-DC converter topology is based on a new conceptual secondary-side series resonant principle and its inherent nature. All the active power switches on the HFTR primary side can achieve lossless capacitive snubber-based zero-voltage switching (ZVS) with the aid of transformer parasitic inductances. Moreover, passive power switches on its secondary side can also perform ZVS and zero-current switching (ZCS) transitions for input voltage and load variations. First, the operation principle of the newly proposed DC-DC converter and some of its noteworthy features are described in this paper on the basis of the results of analysis by simulation. Then, the experimental setup of the DC-DC converter with an output of 5 kW treated here is demonstrated and its experimental results are discussed from a practical viewpoint. Finally, some comparative evaluations between simulation and experimental data are discussed and considered, together with future works. Keywords-component; DC-DC power converter, full-bridge topology, high-frequency transformer link, secondary-side LC resonant principle, primary-side ZVS, secondary-side ZCZVS, photovoltaic generation system I. INTRODUCTION A variety of collaborative developments on renewable, sustainable energy conversion devices technologies and advanced power electronics are urgently required toward the concrete realization of a global zero-carbon society. Among the studies related to energy electronics, the effective utilization of clean PV generating power and energy with the aid of recently developed energy storage devices such as batteries and/or capacitors have attracted special interest in the fields of power electronic distributed power supply system applications and DC-feeding smart grids. With this background, the development of next-generation highefficiency, high-power, high-performance solar converters is Fig. 1. Overview of utility-grid-tied photovoltaic (PV) system with high-frequency isolation and circuit diagram of the new phase-shift, soft-switching, pulse-modulated, full-bridge DCDC converter, which is based on the secondary-side series LC resonant principle. practically needed, which include high-frequency-switching, pulse-modulated DC-DC converters and utility-interactive, sinewave-modulated inverters based on digital control schemes. In particular, front-end, high-power, high-efficiency, highfrequency-switching boost DC-DC power converters such as non-isolated and isolated circuit topologies have been considered and discussed for use with solar power converters in order to improve their efficiency and control performances including the noise issue. We have proposed several circuit topologies for high-frequency-switching DC-DC high-power converter circuits operating under the conditions of soft commutation schemes for high-power industrial applications [1-3]. We have also developed a utility-grid-tied three-phase sinewave inverter operating with a high-efficiency control strategy [4]. To further decrease the power consumption, an advanced high-efficiency and high-power soft-switching DCDC converter topology with a high-frequency transformer link is proposed as a new power-electronics technology, which is based on the secondary-side LC resonant circuit principle for the front-end solar converter in PV generation systems. Also, studies on a variety of DC-DC converters with a highfrequency transformer have been carried out with the aim of increasing their efficiency and power density [5-15]. These converters include series-resonant, soft-switching DC-DC converters with a high-frequency transformer [14-15]. In these studies, a DC-DC converter utilizes the leakage inductance of the transformer for energy storage and/or soft commutation. However, although leakage inductance is useful for realizing a soft-switching DC-DC converter, a large leakage inductance of more than 2 μH or the presence of parasitic capacitance of more than 1 μF decreases the magnetic coupling coefficient of the transformer. This leads to not only a reduction in the efficiency of the high-frequency transformer but also an increase in the surge voltage applied to the high-frequency full-bridge inverter circuit included in this DC-DC converter with a high-frequency transformer. In addition, it is extremely difficult to use some series-resonant DC-DC converters that utilize the leakage inductance of a transformer in high-voltage and high-power applications with power above 1 kW owing to the reduced power transmission efficiency from the primary side to the secondary side. In this paper, we present a high-power, improvedefficiency, phase-shift, soft-switching, pulse-modulated fullbridge DC-DC converter with a high-frequency transformer stage and a front-end boost converter cascade stage, which includes a soft-switching full-bridge diode rectifier operating on the basis of the resonant operating principle and the inherent nature of the secondary-side LC series resonant circuit. This new DC-DC power converter, which is suitable for solar converters, can achieve not only a soft-switching transition based on ZVS on the primary side but also ZVS and ZCS commutation for the full-bridge diode rectifier on the secondary side. The operating principle of this DC-DC converter in a periodic steady state is described by considering switching-mode equivalent circuits and the results of analysis by simulation, along with its inherent notable features compared with those of conventional converters. The simulated operating voltage and current waveforms are comparatively illustrated with experimental waveforms. The actual efficiency versus output power characteristics and power loss analysis are demonstrated experimentally. The practical effectiveness of the proposed converter for PV generation systems is confirmed and verified by means of 5 kW setup implementation and simulation analysis. II. NOVEL TYPE SOFT-SWITCHING DC-DC CONVERTER A. Circuit Description Figure 1 shows the proposed high-frequency transformer link, phase-shift, soft-switching, pulse-modulated, full-bridge DC-DC converter with a front-end boost converter cascade stage that incorporates a soft-switching full-bridge rectifier operating with the secondary-side LC resonant principle. The LC resonant components are located across the output diode rectifier. This high-frequency isolated DC-DC converter designed for PV generation systems can operate under the ZVS condition of the primary-side active switches S1 - S4 in the Hbridge arms with the aid of a lossless capacitor, a leakage inductor Ll and the magnetizing inductance Lm of a twowinding high-frequency transformer with a ferrite core. On the other hand, the passive switches in the secondaryside full-bridge rectifier can also operate under the principle of ZVS and ZCS transitions due to the secondary-side LC resonant circuit property. B. Principle of Converter Operation Figure 2 illustrates the relevant operating voltage and current waveforms during a complete switching period for the gate-driving pulse sequences. The switching operation modes of the soft-switching full-bridge DC-DC converter with a high-frequency transformer are divided into six operations modes from mode 1 to mode 6 in accordance with the operational timing points t0 to t6. As can be seen in Fig. 3, the operation principle is described using equivalent circuits corresponding to each operating mode. • Mode 1 (t0 - t1): During the active state, the corresponding set of primary switches and secondary rectifier diodes (S2, S3 and D2, D3) conduct simultaneously so that the secondary voltage and current have the same polarity. The output power is delivered by applying a DC source to the load. A positive voltage with magnitude Vin is applied to the high-frequency transformer. Both VS1 and VS4, the voltages across S1 and S4, respectively, are also equal to the source voltage Vin. • Mode 2 (t1 - t2): The turn-off signal is applied to S3 at time t1. After S3 is turned off, VS1 begins to decrease gradually because the capacitor parallel with S1, previously charged to the source voltage Vin, discharges linearly to zero. At the same time, the capacitor parallel with S3, previously discharged to zero, charges linearly toward a positive voltage. Therefore, the low-side switch S3 is able to be turned off with ZVS due to current flowing into the capacitor parallel with S3. On the other hand, the diode currents (iD2, iD3) form a sinusoidal wave that approaches zero so that not only D2 but also D3 can be easily turned off with extremely soft recovery during this period. • Mode 3 (t2 - t3): On the other hand, the current through the secondaryside diodes (D1 and D4) starts to flow after VD1 and VD2 become equal to zero at the same time when both VS2 and VS3, the voltages across S2 and S3, respectively, reach the source voltage Vin. At time t4, the primary current still flows through the diode parallel with S1 and S4 (DS1 and DS4) while the turn-on signal is applied to S1. • Mode 5 (t4 - t5): The current through diodes DS1 and DS4 decreases gradually toward zero as the secondary-side current through D1 and D4 increases. At time t5, both S1 and S4 are simultaneously turned on with ZCS. • Fig. 2. Operating voltage and current waveforms of soft-switching, high-frequency transformer link, phase-shift, full-bridge DCDC converter based on the secondary-side LC resonant principle. After the capacitor voltage VS1 reaches zero, the diode parallel with S1 (DS1) starts to conduct and clamps the voltage on the high-side switch S1 at zero. Consequently, the voltage across S3 is clamped at the source voltage Vin. On the other hand, the turn-off gate pulse signal is applied to S2 at time t2. After S2 is turned off, VS4 begins to decrease gradually because the capacitor parallel with S4, previously charged to the source voltage Vin, discharges linearly to zero. At the same time, the capacitor parallel with S2, previously discharged to zero, charges linearly toward a positive voltage. Therefore, the high-side switch S2 is turned off with almost ZVS due to current flowing into the capacitor parallel with S3. Although all primary switches (S1 - S4) are turned off, the primary current is maintained in the same direction during this state. • Mode 6 (t5 - t6): The sinusoidal resonant current flows through the primary-side active switches S1 and S4 and the winding in the primary side of the high-frequency transformer. The current through the secondary-side diodes D1 and D4 and the secondary-side winding of the transformer also forms a sinusoidal resonant wave. The current through the primary side lags behind the voltage, while the phase difference between the voltage and current through the secondary side is close to zero, because the resonant capacitor located between the transformer and the full-bridge diode rectifier acts to form a leading current. This behavior is effective for improving the converter efficiency. In other words, there is no phase difference between the voltage and current on the secondary side, so that diodes in this side are able to be turned off without generating a reverse recovery current. In addition, all the diodes parallel with the primary-side active switches utilize the lagging current during freewheeling states and can be turned off with zero reverse recovery current at time t5. C. Unique Features The specific advantages of the proposed DC-DC converter in Fig. 1 are as follows. (1) Higher conversion efficiency (98%, 380 V DC, 3 kW output) among high-power isolated converters. (2) Utilization of the high-efficiency small-sized transformer with less leakage inductance and parasitic capacitance. (3) Minimum reverse recovery current switching loss in the diode full bridge stage. (4) Primary-side ZVS transition of all the active switches. (5) Secondary-side ZVS and ZCS transition of all the passive switches. (6) Flexible design with high voltage conversion ratio. Mode 4 (t3 - t4): (7) Ground leakage current protection from PV panel to power conversion circuit. Similarly to in Mode 3, current begins to flow in diode DS4 and clamps the voltage on the bottom switch S4 at zero after the capacitor voltage VS1 reaches zero. (8) Easy to connect a front-end boost converter that can operate MPPT with high efficiency. III. CONVERTER SIMULATIONS Table 1. Design specifications and circuit parameters Real-time-based computer simulations were carried out using PSIM version 9.0 to clarify the operation of the converter under constant loading conditions. Figure 4 shows the waveforms of the gate-driving pulse signals (a) (b), the output rectifier (c), the MOSFET primary switch (d), the transformer secondary current (e) and the voltage across the resonant capacitor connected in series with the transformer in the secondary side (VCr) and the inductor current, which composes the output filter connected to the load (iLout) (f) in the case of 5 kW output. As shown in Fig. 4 (c), diode D1 is turned off with ZVS and turned on with ZCS. As shown in Fig. 4 (d), switch S1 is turned off after iS1 reaches zero due to the capacitor parallel with it. The current flowing through the transformer forms the sinusoidal wave due to the series LC resonant circuit, as depicted in Fig. 4 (e). Figure 4 (f) indicates the energy commutation between the resonant capacitor (1/2CV2) and the resonant inductor (1/2Li2) connected to the output diode rectifier. IV. EXPERIMENTAL RESULTS AND DISCUSSION A 380-V-input, DC 5 kW, soft-switching, phase-shift, pulse modulated, full-bridge DC-DC converter with a soft-switching, full-bridge diode rectifier operating on the basis of the secondary-side LC resonant topology was built and tested in an experiment. The design specifications and circuit parameters of the converter are listed in Table 1. The measured voltage and current waveforms of this prototype converter are illustrated in Fig. 7. Comparing Fig. 7 with Fig. 4 (c), it can be seen that these observed voltage and current waveforms are in good agreement with the simulated waveforms. Item Symbol Value Unit DC input voltage (from boost converter) Vin 380 - 388 V DC output voltage Vout 380 V Maximum input power Pin 5.5 kW Switching frequency fsw 30.6 kHz Switching period Ts 16.33 μs Phase shift time Tφ 0.95 μs Dead time Td 1.6 μs Leakage inductance of high-frequency transformer Ll < 1.3 μH Magnetizing inductance of high-frequency transformer Lm 640 μH Magnetic coupling coefficient of high-frequency transformer k 0.998 - Inductance of output filter (series resonant inductor) Lout 20 μH Capacitance of capacitors parallel with transistors CS1 - CS4 5 nF Capacitance of input/output capacitors Cin, Cout 50 μF Capacitance of series resonant capacitor Cr 0.88 μF Turn ratio of high-frequency transformer N1 : N2 1:1 - Item Symbol Product type Primary-side MOSFET switches S1 - S4 FCA76N60N Secondary-side rectifier diodes D1 - D4 RHRP3060 Core material of high-frequency transformer - ferrite (PQ107) The measured efficiency versus output power characteristic under a constant output voltage and various specifications is (a) S W 1 S W 3 S W 2 S W 4 1 0 . 0 . 0 . 0 . 8 6 4 S2 2 0 (b) 1 0 . 8 0 . 6 0 . 4 0 . 2 (C) S3 S4 S2 S1 S4 0 0 . 1 9 9 9 4 ID1*20 0 . 1 9 9 9 5 0 . 1 9 9 9 6 T i m e ( s ) 0 . 1 9 9 9 7 0 . 1 9 9 9 8 0 . 1 9 9 9 9 V_D1 400 VD1 (V) 200 iD1×20 (A) VG_S2 (10 V/Div) 0 (d) 600 I_S1*20 V_S1 400 VS1 (V) iS1×20 (A) 200 0 -200 (e) VD1 Itrans_pri (100 V/Div) 20 itr (A) 0 -20 (f) 150 100 50 0 -50 -100 I_Lout*5 0.19994 Vcap VS2 (250 V/Div) ID1 (5 A/Div) iLout×5 (A) Vcap (V) 0.19995 0.19996 Time (s)(s) Time 0.19997 0.19998 0.19999 Fig. 4. Simulated results of (a) gate driving signals S1 and S3, (b) gate driving signals S2 and S4, (c) voltage and current of D1, (d) voltage and current of S1, (e) resonant current of high-frequency transformer and (f) inductor current and capacitor voltage of LC resonant circuit under the conditions of 380 V and 5.5 kW. Fig. 7. Experimental waveforms of gate-source voltage of S2 (VG_S2, 10 V/div), drain-source voltage of S2 (VS2, 250 V/div), current of diode D1 (ID1, 5 A/div) and voltage of anode and cathode (VD1, 100 V/div). (a) Efficiency (%) of fsw = 43.3 kHz became shorter than that of fsw = 30.6 kHz while the dead time was fixed at 1.6 μs in both conditions. Without wiring for measurement 98.5 98 97.5 97 96.5 With wiring for measurement 96 95.5 95 Vin = 380 V fsw = 30.6 kHz Lout = 20 μH 94.5 94 93.5 93 0 1 2 3 4 5 6 7 Output Power (kW) (b) Efficiency (%) fsw = 43.3 kHz 98.5 98 97.5 97 96.5 fsw = 30.6 kHz 96 Vin = 380 V Lout = 20 μH 95.5 95 0 1 2 3 4 5 6 Output Power (kW) Fig. 8. Measured efficiencies of the trial soft-switching, fullbridge DC-DC power converter with secondary-side series LC resonant rectifier as a function of the output power. illustrated in Fig. 8. As shown in Fig. 8 (a), the efficiency reaches a maximum value of 98% at an output power of 3-4 kW, as indicated by white diamonds. Above this power range, the efficiency slightly decreases, mainly because the total conduction loss of the converter increases with the increasing load current. However, 97.8% efficiency can still be obtained at 5.2 kW output. Efficiency of above 97% was measured for outputs of 1-5.2 kW. Figure 8 also depicts the efficiency as black circles. Under the measurement conditions, the terminals of these components were connected directly to the measuring instruments by lengthening cables to examine the losses of each component composing the soft-switching DC-DC converter with the high-frequency transformer. The maximum decrease in efficiency of 0.3% was measured at an output power of over 3 kW because of the increased conduction loss. Fig. 8 (b) shows that the peak of converter efficiency shifts by changing switching frequency. In the condition of fsw = 43.3 kHz, the efficiency reaches a maximum value of 98.1% at an output power of 1.5 kW, as indicated by black circles. However, the decrease in efficiency of 0.4% was measured at an output power above 5 kW, mainly because the PWM width By connecting the input and output terminals of each power circuit component composing the phase-shift, soft-switching, pulse-modulated, full-bridge DC-DC converter with a highfrequency transformer to the measuring instrument, the input and/or output power of each component can be measured directly so that the losses of these components can also be investigated. The power loss of the components of the converter was analyzed, the result of which is illustrated in Fig. 9. As can be seen in Fig. 9, the sum of these losses is increased with increasing output power. Under the experimental condition of Vin = 380 V, the total loss of the soft-switching, full-bridge DC-DC converter with a secondary-side resonant circuit is increased from 30.7 W to 144 W (approximately a 4.7-fold increase) with increasing output power from 0.5 kW to 5.5 kW (11-fold growth). In the MOSFET full-bridge circuit, the loss is increased from 24.5 W to 81 W (3.3-fold growth). Similarly, 8.8-fold (from 4.1 W to 36 W) and 12.9fold (from 2.1 W to 27 W) increases in the power loss were calculated for the HF transformer and the rectifier with the output filter, respectively. Figure 10 shows the loss ratio of the elements composing the converter. The primary-side MOSFET switches that comprise the full-bridge circuit in the soft-switching DC-DC converter account for 80% of the total power consumption at output powers of 1.1 kW or less and about 60% of the consumption at 1.7 kW or more. In addition, the MOSFET switches also account for 56.3% of the total power loss at a full load. These results indicate that most of the total converter loss is due to the full-bridge circuit, which consists of MOSFET switches. The loss ratio of the HF transformer decreases from about 30% to 25% with increasing output power above 1.6 kW. In contrast, the loss ratio of the rectifier with the filter grows from 7.5% to 18.8% due to increasing conduction loss. Comparing Fig. 8 (a) and Fig. 10, the results indicate that the effect of the increasing loss of the rectifier with the filter on the efficiency degradation of the converter becomes more significant as the output power increases. V. CONCLUSION In this paper, a new high-power, high-efficiency, phase-shift, soft-switching-transition, pulse-modulated DC-DC power converter with a high-frequency transformer for PV generation systems has been presented, which is based on the secondaryside LC series resonant circuit principle. The operation principle of this new DC-DC converter in a steady state has been schematically described using the results of analysis by simulation and confirmed experimentally. This new conceptual high-frequency link is achieved by highefficiency power conversion processing based on the secondary-side LC resonant principle. The key operating waveforms obtained by simulation and experimentally have been discussed and evaluated in detail. The actual efficiency versus output power characteristics have also been demonstrated and discussed. (3) A feasibility study of this DC-DC converter for utilitygrid-tied PV generation systems. Loss (W) 160 140 120 21.0 80 MOSFET switches 2.1 4.1 2.4 4.7 24.5 28.2 0.5 1.1 3.2 12.8 36.0 12.9 31.0 REFERENCES 24.0 7.7 3.2 40 20 (4) The integration of a multiphase DC-DC converter system and its practical evaluation for a power electronic building block. 27.0 HF-Transformer with resonant capacitor 100 60 Rectifier + Output filter Vin = 380 V fsw = 30.6 kHz Lout = 20 µH [1] 19.0 15.3 73.0 81.0 59.0 26.7 31.3 1.7 2.1 41.4 0 3.0 4.1 5.1 5.6 Output Power (kW) Fig. 9. Results of power loss analysis of full-bridge inverter circuit consisting of MOSFET primary switches, highfrequency transformer and diode rectifier with output filter. Loss (p. u.) [2] [3] Rectifier + Output filter 1 [4] 0.9 0.8 0.7 0.6 [5] 0.5 0.4 0.3 0.2 0.1 HF-Transformer with resonant capacitor Vin = 380 V fsw = 30.6 kHz Lout = 20 µH [6] MOSFET switches 0 [7] 0.5 1.1 1.7 2.1 3.0 4.1 5.1 5.6 Output Power (kW) [8] Fig. 10. 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