Introduction to Laplace Transforms Definition of the Laplace Transform One-sided Laplace transform: F ( s) L f (t ) 0 f (t )e st l Some functions may not have Laplace transforms but we do not use them in circuit analysis. Choose 0- as the lower limit (to capture discontinuity in f(t) due to an event such as closing a switch). dt The Step Function ? Laplace Transform of the Step Function Lu( t ) 0 u( t )e st 1 st - e s 0 st e dt 0 dt 1 s The Impulse Function The sifting property: f (t ) (t a )dt f (a ) The impulse function is a derivative of the step function: du(t ) (t ) dt t ( x )dx u(t ) ? Laplace transform of the impulse function: L ( t a ) 0 ( t a )e For a 0, L ( t ) 1 st dt e as Laplace Transform Features 1) Multiplication by a constant L f ( t ) F ( s ) L Kf ( t ) KF ( s ) 2) Addition (subtraction) L f1 ( t ) F1 ( s ), L f 2 ( t ) F2 ( s ), L f1 ( t ) f 2 ( t ) F1 ( s ) F2 ( s ) 3) Differentiation df ( t ) L sF ( s ) f (0 ), dt d 2 f ( t ) 2 L s F ( s ) sf (0 ) f (0 ) 2 dt d n f ( t ) n n 1 n 2 L s F ( s ) s f (0 ) s f (0 ) n dt sf ( n 2) (0 ) f ( n 1) (0 Laplace Transform Features (cont.) 3) Differentiation df ( t ) L sF ( s ) f (0 ), dt d 2 f ( t ) 2 ) (0 f ) (0 sf ) s ( F s L 2 dt . . . d n f ( t ) n n 2 n 1 ) (0 f s ) (0 f s ) s ( F s L n dt sf ( n 2) (0 ) f ( n 1) (0 ) Laplace Transform Features (cont.) 4) Integration L t 0 F ( s) f ( x )dx s 5) Translation in the Time Domain L f (t a )u(t a ) e as F ( s ), a 0 Laplace Transform Features (cont.) 6) Translation in the Frequency Domain L e at f (t ) F ( s a ) 7) Scale Changing 1 s L f (at ) F , a a a 0 Laplace Transform of Cos and Sine ? Laplace Transform of Cos and Sine Lcos t .u( t ) 0 cos t .u( t )e st e 0 j t dt 0 cos te st dt e j t st 1 ( s j )t ( s j ) t e dt [ 0 e dt 0 e dt ] 2 2 1 1 e ( s j )t 2 s j 0 1 1 e ( s j )t 2 s j 1 1 1 1 s 2 2 s j 2 s j s 2 Lsin t .u(t ) 2 2 s 0 Name Time function f(t) Laplace Transform Unit Impulse (t) u(t) t tn e-at t n e-at sin(bt) cos(bt) e-at sin(bt) e-at cos(bt) t sin(bt) t cos(bt) Unit Step Unit ramp nth-Order ramp Exponential nth-Order exponential Sine Cosine Damped sine Damped cosine Diverging sine Diverging cosine 1 1/s 1/s2 n!/sn+1 1/(s+a) n!/(s+a)n+1 b/(s2+b2) s/(s2+b2) b/((s+a)2+b2) (s+a)/((s+a)2+b2) 2bs/(s2+b2)2 (s2-b2) /(s2+b2)2 Some Laplace Transform Properties (t) F(s) A (t) A F(s) 1(t) ± 2(t) F1(s) ± F2(s) Property Scaling Linearity 1 s F a a a0 Time Scaling (a·t) Time Shifting (delay) (t–t0) u(t–t0) e–s·t0 F(s) t00 Frequency Shifting e–a·t (t) F(s+a) Time Domain Differentiation d f (t ) dt s F(s) – (0) Frequency Domain Differentiation t (t) t 0 Time Domain Integration t Convolution 0 f ( ) d f1 ( ) f 2 ( t ) d d F ( s) ds 1 F ( s) s F1(s) F2(s) Inverse Laplace Transform Partial Fraction Expansion Step1: Expand F(s) as a sum of partial fractions. Step 2: Compute the expansion constants (four cases) Step 3: Write the inverse transform Example: s6 2 s( s 3)( s 1) K3 K1 K2 K4 s6 2 2 s s 3 s1 s( s 3)( s 1) ( s 1) 1 s6 L 2 s( s 3)( s 1) K1 K 2e 3 t K 3te t K 4e t u( t ) Distinct Real Roots K3 K2 96( s 5)( s 12) K1 F ( s) s( s 8)( s 6) s s8 s6 96( s 5)( s 12) 96(5)(12) K1 sF ( s ) s 0 s 120 s( s 8)( s 6) s 0 8(6) 96( s 5)( s 12) 96( 3)(4) K 2 ( s 8)F ( s ) s 8 ( s 8) 72 s( s 8)( s 6) s 8 8( 2) K 3 ( s 6)F ( s ) s 6 ( s 6) 96( s 5)( s 12) 96( 1)(6) 48 s( s 8)( s 6) s 6 6(2) 120 48 72 F ( s) s s6 s8 f ( t ) (120 48e 6 t 72e 8 t )u( t ) Distinct Complex Roots 100( s 3) 100( s 3) F ( s) 2 ( s 6)( s 6 s 25) ( s 6)( s 3 j 4)( s 3 j 4) K3 K1 K2 s 6 s 3 j4 s 3 j4 100( s 3) 100( 3) K1 2 12 25 s 6 s 25 s 6 K2 100( s 3) 100( j 4) ( s 6)( s 3 j 4) s 3 j 4 (3 j 4)( j 8) 6 j 8 10e j 53.130 100( s 3) 100( j 4) K3 ( s 6)( s 3 j 4) s 3 j 4 (3 j 4)( j 8) 6 j 8 10e j 53.130 Distinct Complex Roots (cont.) 12 10 53.130 10 53.130 F ( s) s6 s 3 j4 s 3 j4 f ( t ) ( 12e 10e 6 t 10e j 53.130 (3 j 4) t 10e e 3 t (e j 53.130 (3 j 4) t e 10e j (4 t 53.130 ) e 10e j 53.130 (3 j 4) t j 53.130 (3 j 4) t e j (4 t 53.130 ) ) 20e 3 t cos(4t 53.130 ) f ( t ) [12e 6 t 20e 3 t cos(4t 53.130 )]u( t ) e )u( t ) Whenever F(s) contains distinct complex roots at the denominator as (s+-j)(s++j), a pair of terms of the form K K* s j s j appears in the partial fraction. Where K is a complex number in polar form K=|K|ej=|K| 0 and K* is the complex conjugate of K. The inverse Laplace transform of the complex-conjugate pair is * K K 1 L s j s j 2K e t cos( t ) Repeated Real Roots K3 K2 K4 100( s 25) K 1 F ( s) 3 3 2 s ( s 5) s5 s( s 5) ( s 5) 100( s 25) 100(25) K1 20 3 125 ( s 5) s 0 100( s 25) 100(20) K2 400 s 5 s 5 d s ( s 25) 3 K 3 ( s 5) F ( s ) 100 100 2 s 5 ds s s 5 1 d2 1 2 s(25) 3 K4 ( s 5) F ( s ) 100 20 2 4 s 5 2 ds 2 s s 5 20 400 100 20 F ( s) 3 2 s ( s 5) s5 ( s 5) f ( t ) [20 200t 2e 5 t 100te 5 t 20e 5 t ]u( t ) Repeated Complex Roots 768 768 F ( s) 2 2 ( s 6 s 25) ( s 3 j 4)2 ( s 3 j 4)2 K1 K1* K2 K 2* 2 2 ( s 3 j 4) ( s 3 j 4) ( s 3 j 4) ( s 3 j 4) 768 K1 ( s 3 j 4)2 768 12 2 ( j 8) s 3 j 4 d 768 2(768) K2 2 ds ( s 3 j 4) s 3 j 4 ( s 3 j 4)3 2(768) 0 j 3 3 -90 ( j 8)3 s 3 j 4 12 12 F ( s) 2 2 ( s 3 j 4) ( s 3 j 4) 3 -900 3 900 s 3 j4 s 3 j4 f ( t ) [ 24te 3 t cos 4t 6e 3 t cos(4t 90 )]u( t ) 0 Improper Transfer Functions An improper transfer function can always be expanded into a polynomial plus a proper transfer function. s 4 13 s 3 66 s 2 200 s 300 F ( s) s 2 9 s 20 30 s 100 2 s 4 s 10 2 s 9 s 20 20 50 2 s 4 s 10 s4 s5 d (t ) d ( t ) 4 t 5 t f (t ) 4 10 ( t ) ( 20 e 50 e )u( t ) 2 dt dt 2 POLES AND ZEROS OF F(s) The rational function F(s) may be expressed as the ratio of two factored polynomials as K ( s z1 )( s z2 ) ( s zn ) F ( s) ( s p1 )( s p2 ) ( s pm ) The roots of the denominator polynomial –p1, -p2, ..., -pm are called the poles of F(s). At these values of s, F(s) becomes infinitely large. The roots of the numerator polynomial -z1, -z2, ..., -zn are called the zeros of F(s). At these values of s, F(s) becomes zero. 10( s 5)( s 3 j 4)( s 3 j 4) F ( s) s( s 10)( s 6 j 8)( s 6 j 8) The poles of F(s) are at 0, -10, -6+j8, and –6-j8. The zeros of F(s) are at –5, -3+j4, -3-j4 num=conv([1 5],[1 6 25]); den=conv([1 10 0],[1 12 100]); pzmap(num,den) Initial-Value Theorem The initial-value theorem enables us to determine the value of f(t) at t=0 from F(s). This theorem assumes that f(t) contains no impulse functions and poles of F(s), except for a first-order pole at the origin, lie in the left half of the s plane. lim f (t ) lim sF ( s) t 0 s 100( s 3) F ( s) 2 ( s 6)( s 6 s 25) f ( t ) [12e 6 t 20e 3 t cos(4t 53.130 )]u( t ) Final-Value Theorem The final-value theorem enables us to determine the behavior of f(t) at infinity using F(s). lim f ( t ) lim sF ( s ) t s 0 The final-value theorem is useful only if f(∞) exists. This condition is true only if all the poles of F(s), except for a simple pole at the origin, lie in the left half of the s plane. 100( s 3) lim F ( s ) lim s 0 2 s 0 s 0 ( s 6)( s 6 s 25) lim f ( t ) lim[12e 6t 20e 3t cos(4t 53.130 )]u( t ) 0 t t