> REPLACE THIS LINE WITH YOUR PAPER IDENTIFICATION NUMBER (DOUBLE-CLICK HERE TO EDIT) < 1 Design and Testing of a Self-Powered 3-D Integrated SOI CMOS System Zeynep Dilli, Student Member, IEEE, Neil Goldsman, Martin Peckerar and George Metze Abstract—A self-powering 3-D integrated circuit built using a SOI CMOS process is presented. Design questions and bottlenecks are discussed, with simulation results demonstrating the circuit as a feasible proof-of-concept system. After a review of measurement issues, test results are given, which demonstrate the system operating as designed: A photodiode array powering an oscillator. Index Terms—CMOS wireless sensor networks, photocells, photodiodes, self-powered devices, SOI. I. INTRODUCTION W E present the design and testing of a three-dimensional integrated circuit (3-DIC), incorporating energy harvesting and storage units along with a functional block. In the context of wireless sensor network technology, a vivid question is how to power their individual nodes. Low-power designs, and integrated power sources or self-powering, are items of interest [1]. 3-D integration is promising for this technology, with its possibilities of tighter system-level integration, lower noise coupling between subsystems and lower connection parasitics; thus we explore a 3-D implementation. Some approaches to power-harvesting from ambient energy are thermoelectric generators, rectifying antennas and photocells [2, 3]. Our system uses photocells, designed as photodiode arrays with a charge-integrating capacitor. Our power-harvesting structure does not take up active silicon space meant for functional electronics thanks to chip stacking by 3-D integration. II. SYSTEM OVERVIEW Figure 1 displays the placement of different elements in our stack: The bottom tier: Functional elements; specifically a local oscillator and an output buffer. The middle tier: Storage elements; specifically an integrating capacitor. The top tier: Sensor elements; specifically an array of photodiodes for power-harvesting. We can visualize different implementations of these general Zeynep Dilli, Neil Goldsman and Martin Peckerar are with the Department of Electrical and Computer Engineering, University of Maryland College Park, College Park, MD 20742 (e-mail: dilli@eng.umd.edu). George Metze is with the Laboratory for Physical Sciences, College Park, MD, 20740. Fig. 1. A 3-D system design concept: Sensor, storage and electronics layers. Elements in our specific design are shown here. functions. Data sensors (e.g. photosensors or antenna circuitry) as well as power harvesters could be placed on the top tier, with data storage and preliminary/mixed-signal circuits (e.g. A/D converters) on the second tier and back end/data processing circuitry on the bottom layer. Our design is intended for the novel three-tiered 3-DIC process of MIT Lincoln Labs, based on their 0.18 μm fullydepleted silicon-on-insulator (FDSOI) process. Each tier is individually fabricated as a planar IC. For the final assembly, the top two tiers are flipped over for stacking, their handle wafers removed. Dense tungsten vias through intertier oxide layers provide tier-to-tier connections, with bonding pads obtained by overglass cuts from the top tier backside to the first metal layer. III. PHOTODIODE DESIGN AND LAYOUT The main concern in the design of the photodiode array in our system is obtaining the maximum photocurrent within our assigned design area of 250 μm by 250 μm. A theoretical calculation [6] yields an expectable ~6.6 nA photocurrent under red light with 1000 W/m2 intensity, the prominent bottleneck being the 50 nm silicon depth of this SOI process, allowing only about 1.7% absorption. We designed two photodiode types with the available layers in the process. The first type uses ``intrinsic'' (very low-doped > REPLACE THIS LINE WITH YOUR PAPER IDENTIFICATION NUMBER (DOUBLE-CLICK HERE TO EDIT) < 2 Fig. 3. Simulation results. The inset depicts the beginning of the oscillation (between 320 μs and 360 μs) and the main figure body shows full oscillation. In both the inset and the main figure, the voltage scale is between -50 mC and 300 mV, and the dashed line is the rail voltage, which ha sreached a steady state of about 242 mV in this simulation. The lighter solid line is the ring oscillator output feeding the buffer and the thick solid line is buffer output. IV. CIRCUIT ANALYSIS AND SIMULATIONS Fig. 2. Top: The pin- (left) and pn- (right) diode layouts (not to scale). Bottom: The fabricated chip, top layer microphotograph. To the left, top: The VDD pad, bottom: the GND pad. The pin-diode array is next to the VDD pad. To the right, the output pad. The rest is the annular pn-diode array. The vertical via arrays from the VDD and GND pads to the lower layers are to their right; the vertical via to the output pad from the lower layers is to its top. Lower tiers are somewhat visible, but out of focus, at the edges of the bonding pads, where there is no layout in the top tier. p-type, NA1014 cm-3) silicon and the n-type threshold adjustment implant, ND=51017 cm-3. This pin-diode depletion region width is about 1.5 μm. Making the junction 10 μm wide yields about 99.5 pA per diode. However, this ``intrinsic'' layer is not recommended for use [7]: Its regions are vulnerable to surface accumulation or inversions, which would alter diode operating characteristics. Thus, we do not rely solely on this type of diode, although 52 are present in an array in the final design. The second type is formed by the junction between the nand p-type threshold adjust implants, NA=ND=51017 cm-3. We use an annular layout to maximize junction area and total diode number, 2062 in the final design. Fig. 2 displays the diode layouts and the microphotograph of the fabricated chip. After fabrication, total circuit volume is 250250700 μm3. The functional block of our circuit is a three-stage local oscillator, formed by inverters in a ring-oscillator configuration. We chose minimum-size NMOS transistors to minimize current requirements, the PMOS size set for a midrange switching point. We also have a two stage output buffer. The circuit is displayed in Fig. 1. Fig. 3 shows a simulation of the circuit operation with the output bonding pad as the load (~15 fF) [8]. The photocurrent, charging the storage capacitor Cst, builds up the inverters' rail voltage. Inverter output (and thus, input) voltages follow; at a certain level, the local oscillator has sufficient gain to amplify noise and start oscillation. From this point on all inverters are drawing current, which increases with rising rail voltage until the current consumption balances the photocurrent charging Cst and rail voltage stabilizes. Higher assumed photocurrents in the simulation yield higher rail voltages. In practice, two more factors affect operation. The first is that the rail voltage forward-biasing the diodes too, which then themselves sink some current. Our calculations indicate that this will limit rail voltage, for normal illumination, to below 0.4 V. At the cost of harvested power per area, this problem might be addressed by multiple photodiodes in series or alternate current transfer circuits [9]. The second is the extra load for measurements, discussed below. V. MEASUREMENTS Fabricated chips, received as bare dies, were wire-bonded to open SOIC-type packages. Our layout allows for measuring the rail voltage across the VDD/GND pads and the oscillator/buffer output through the output pad. A. Rail Voltage Measurements Of the seven bonded samples, all exhibit some voltage across Cst, although for some the level is higher than the others. The high level is about 300 mV under the beam from a > REPLACE THIS LINE WITH YOUR PAPER IDENTIFICATION NUMBER (DOUBLE-CLICK HERE TO EDIT) < red laser pointer Pin <330 W/m2 and 40 to 80 mV under a white LED flashlight. Steady voltages around 100 mV were observed in a sunlit room. For the laser pointer Pin, the calculated expected current would be ~5 nA, which in simulations yields a lower rail voltage. The disparity is probably due to multiple absorptions, as light is reflected back from the lower tier metal layers. It is possible to damage samples working at the higher level so that they begin to yield lower voltages, sometimes by toobright illumination. A credible problem is contamination; the more likely cause is pin-junction damage by the forwardbiasing effect and high currents. 3 the input of a non-inverting amplifier of gain $\sim$23, equivalently a 1 pF load. Fig. 4 displays scope screen captures of the amplifier output when the 3-DIC is under low illumination (only fluorescent room lights) and under a laser beam. In the former case, the DC level of the observed noise signal is at about 40 mV. In the latter case, the observed peak amplitude varies between 70130 mV, with the bottom level at ~39 mV. Taking the amplifier gain into account, this indicates a 3-DIC buffer output amplitude of the order of 4.3 mV, consistent with simulation results for a 1 pF load. The oscillation frequency is 1.8 MHz. Thus we demonstrate that the oscillator is indeed operating and the steady rail voltages presented in the previous section are not merely the photocurrent discharging from Cst through the voltmeter. VI. CONCLUSION We have demonstrated the operation of a self=powered three-dimensional integrated circuit. In the design stage, our simulations had shown this system as a feasible self-powered system proof-of-concept. The 3-DIC functions satisfactorily within the design limitations, the deviations from the expected behavior being mainly favorable and explainable by using the physical realities of the chip. REFERENCES [1] [2] [3] [4] [5] [6] [7] [8] Fig. 4. Top: Amplifier output with 3-DIC under low-level illumination. The maximum signal amplitude is ~10 mV, with a ~40 mV DC component. Bottom: With 3-DIC under laser pointer light. The maximum signal amplitude is 130 mV, and dominant frequency is 1.8 MHz. B. Oscillator Output Inherent current limitations prohibited the design of a buffer capable of driving high capacitive or low resistive loads. In particular, our active scope probe specifies a load resistance of 20K and capacitance of 1 pF, which when included in simulations allows no meaningful output voltage level. Therefore, to be able to observe the self-powered circuit operation, we added an external amplifier stage built around a commercial low input bias current CMOS op-amp (LMH6601). The oscillator buffer output was connected to [9] M. Philipose, J.R. Smith, B. Jiang, A. Mamishev, K. Sindora-Rajan, “Battery-Free wireless identification and sensing,” Pervasive Computing, v. 4., no. 1, pp. 37-45, Jan-Mar 2005. M. Strasser, R. Aigner, C. Lauterbach, T.F. Sturm, M. Franosch, G. Wachutka, “Micromachined CMOS thermoelectric generators as onchip power supply,” in 12th Int. Conf. on Solid State Sensors, Actuators and Microsystems, Boston, June 8-12 2003, pp. 45-48. J. Zbitou, M. Latrach, S. 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