UNIT-II Comparators, Voltage level detectors, Schmitt Triggers, linear half-wave rectifiers,
precision rectifiers, peak detectors, Sample and Hold circuits, AC to DC converters, deadzone circuits, Clippers, Clampers. Filters: Design of I, II and higher order filters. Butterworth,
Chebyshev, Low pass, High pass, Band pass, Wide band, Narrow band, notch filters,
Universal filters.
Comparator
In electronics, a comparator is a device that compares two voltages or currents and outputs a
digital signal indicating which is larger. It has two analog input terminals
binary digital output
and
and one
. The output is ideally
A comparator consists of a specialized high-gain differential amplifier. They are commonly
used in devices that measure and digitize analog signals, such as analog-to-digital converters
(ADCs), as well as relaxation oscillators.
Differential voltage
The differential voltages must stay within the limits specified by the manufacturer. Early
integrated comparators, like the LM111 family, and certain high-speed comparators like the
LM119 family, require differential voltage ranges substantially lower than the power supply
voltages (±15 V vs. 36 V).
or, when powered from a unipolar TTL/CMOS power supply:
Specific rail-to-rail comparators with p-n-p input transistors, like the LM139 family, allow
input potential to drop 0.3 volts below the negative supply rail, but do not allow it to rise
above the positive rail.[2] Specific ultra-fast comparators, like the LMH7322, allow input
signal to swing below the negative rail and above the positive rail, although by a narrow
DEPARTMENT OF ECS
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margin of only 0.2 V.[3] Differential input voltage (the voltage between two inputs) of a
modern rail-to-rail comparator is usually limited only by the full swing of power supply.
Op-amp voltage comparator
A simple op-amp comparator
An operational amplifier (op-amp) has a well balanced difference input and a very high gain.
This parallels the characteristics of comparators and can be substituted in applications with
low-performance requirements.
In theory, a standard op-amp operating in open-loop configuration (without negative
feedback) may be used as a low-performance comparator. When the non-inverting input (V+)
is at a higher voltage than the inverting input (V-), the high gain of the op-amp causes the
output to saturate at the highest positive voltage it can output. When the non-inverting input
(V+) drops below the inverting input (V-), the output saturates at the most negative voltage it
can output. The op-amp's output voltage is limited by the supply voltage. An op-amp
operating in a linear mode with negative feedback, using a balanced, split-voltage power
supply,
(powered
by
±
VS)
has
its
transfer
function
typically
written
as:
. However, this equation may not be applicable to a comparator
circuit which is non-linear and operates open-loop (no negative feedback)
In practice, using an operational amplifier as a comparator presents several disadvantages as
compared to using a dedicated comparator:
1. Op-amps are designed to operate in the linear mode with negative feedback. Hence,
an op-amp typically has a lengthy recovery time from saturation. Almost all op-amps
have an internal compensation capacitor which imposes slew rate limitations for high
frequency signals. Consequently an op-amp makes a sloppy comparator with
propagation delays that can be as long as tens of microseconds.
2. Since op-amps do not have any internal hysteresis, an external hysteresis network is
always necessary for slow moving input signals.
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3. The quiescent current specification of an op-amp is valid only when the feedback is
active. Some op-amps show an increased quiescent current when the inputs are not
equal.
4. A comparator is designed to produce well limited output voltages that easily interface
with digital logic. Compatibility with digital logic must be verified while using an opamp as a comparator.
5. Some multiple-section op-amps may exhibit extreme channel-channel interaction
when used as comparators.
6. Many op-amps have back to back diodes between their inputs. Op-amp inputs usually
follow each other so this is fine. But comparator inputs are not usually the same. The
diodes can cause unexpected current through inputs.
Working
A dedicated voltage comparator will generally be faster than a general-purpose operational
amplifier pressed into service as a comparator. A dedicated voltage comparator may also
contain additional features such as an accurate, internal voltage reference, an adjustable
hysteresis and a clock gated input.
The LM339 accomplishes this with an open collector output. When the inverting input is at a
higher voltage than the non inverting input, the output of the comparator connects to the
negative power supply. When the non inverting input is higher than the inverting input, the
output is 'floating' (has a very high impedance to ground). The gain of op amp as comparator
is given by this equation V(out)=V(in)
Key specifications
While it is easy to understand the basic task of a comparator, that is, comparing two voltages
or currents, several parameters must be considered while selecting a suitable comparator:
Output type
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A Low Power CMOS Clocked Comparator
Because comparators have only two output states, their outputs are near zero or near the
supply voltage. Bipolar rail-to-rail comparators have a common-emitter output that produces
a small voltage drop between the output and each rail. That drop is equal to the collector-toemitter voltage of a saturated transistor. When output currents are light, output voltages of
CMOS rail-to-rail comparators, which rely on a saturated MOSFET, range closer to the rails
than their bipolar counterparts.[9]
On the basis of outputs, comparators can also be classified as open drain or push–pull.
Comparators with an open-drain output stage use an external pull up resistor to a positive
supply that defines the logic high level. Open drain comparators are more suitable for mixedvoltage system design. Since the output is high impedance for logic level high, open drain
comparators can also be used to connect multiple comparators on to a single bus. Push pull
output does not need a pull up resistor and can also source current unlike an open drain
output.
Schmitt trigger
In electronics a Schmitt trigger is a comparator circuit with hysteresis implemented by
applying positive feedback to the noninverting input of a comparator or differential amplifier.
It is an active circuit which converts an analog input signal to a digital output signal. The
circuit is named a "trigger" because the output retains its value until the input changes
sufficiently to trigger a change. In the non-inverting configuration, when the input is higher
DEPARTMENT OF ECS
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than a chosen threshold, the output is high. When the input is below a different (lower)
chosen threshold the output is low, and when the input is between the two levels the output
retains its value. This dual threshold action is called hysteresis and implies that the Schmitt
trigger possesses memory and can act as a bistable circuit (latch or flip-flop). There is a close
relation between the two kinds of circuits: a Schmitt trigger can be converted into a latch and
a latch can be converted into a Schmitt trigger.
Schmitt trigger devices are typically used in signal conditioning applications to remove noise
from signals used in digital circuits, particularly mechanical switch bounce. They are also
used in closed loop negative feedback configurations to implement relaxation oscillators,
used in function generators and switching power supplies.
The output of a Schmitt trigger (B) and a comparator (A), when a noisy signal (U) is applied.
The green dotted lines are the circuit's switching thresholds. The Schmitt trigger tends to
remove noise from the signal.
Block diagram of a Schmitt trigger circuit. It is a system with positive feedback in which the
output signal fed back into the input causes the amplifier A to switch rapidly from one
saturated
state
to
the
other
when
the
input
:A > 1 is the amplifier gain :B < 1 is the feedback transfer function
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crosses
a
threshold.
Circuits with hysteresis are based on the fundamental positive feedback idea: any active
circuit can be made to behave as a Schmitt trigger by applying a positive feedback so that the
loop gain is more than one. The positive feedback is introduced by adding a part of the output
voltage to the input voltage; so, these circuits contain an attenuator (the B box in the figure
on the right) and a summer (the circle with "+" inside) in addition to an amplifier acting as a
comparator. There are three specific techniques for implementing this general idea. The first
two of them are dual versions (series and parallel) of the general positive feedback system. In
these configurations, the output voltage increases the effective difference input voltage of the
comparator by decreasing the threshold or by increasing the circuit input voltage; the
threshold and memory properties are incorporated in one element. In the third technique, the
threshold and memory properties are separated.
Dynamic threshold (series feedback): when the input voltage crosses the threshold in some
direction the very circuit changes its own threshold to the opposite direction. For this
purpose, it subtracts a part of its output voltage from the threshold (it is equal to adding
voltage to the input voltage). Thus the output affects the threshold and does not impact on the
input voltage. These circuits are implemented by a differential amplifier with series positive
feedback where the input is connected to the inverting input and the output - to the noninverting input. In this arrangement, attenuation and summation are separated: a voltage
divider acts as an attenuator and the loop acts as a simple series voltage summer. Examples:
the classic transistor emitter-coupled Schmitt trigger, op-amp inverting Schmitt trigger, etc.
Modified input voltage (parallel feedback): when the input voltage crosses the threshold in
some direction the circuit changes the very input voltage in the same direction (now it adds a
part of its output voltage directly to the input voltage). Thus the output "helps" the input
voltage and does not affect the threshold. These circuits can be implemented by a singleended non-inverting amplifier with parallel positive feedback where the input and the output
sources are connected through resistors to the input. The two resistors form a weighted
parallel summer incorporating both the attenuation and summation. Examples: the less
familiar collector-base coupled Schmitt trigger, op-amp non-inverting Schmitt trigger, etc.
Some circuits and elements exhibiting negative resistance can also act in a similar way:
negative impedance converters (NIC), neon lamps, tunnel diodes (e.g., a diode with an "N"shaped current–voltage characteristic in the first quadrant), etc. In the last case, an oscillating
DEPARTMENT OF ECS
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input will cause the diode to move from one rising leg of the "N" to the other and back again
as the input crosses the rising and falling switching thresholds.
Two different unidirectional thresholds are assigned in this case to two separate openloop comparators (without hysteresis) driving an RS trigger (2-input memory cell). The
trigger is toggled high when the input voltage crosses down to up the high threshold and low
when the input voltage crosses up to down the low threshold. Again, there is a positive
feedback but now it is concentrated only in the memory cell. Examples: 555 timer, switch
debounce circuit.[3]
A symbol of Schmitt trigger shown with a non-inverting hysteresis curve embedded in a
buffer. Schmitt triggers can also be shown with inverting hysteresis curves and may be
followed by bubbles. The documentation for the particular Schmitt trigger being used must be
consulted to determine whether the device is non-inverting (i.e., where positive output
transitions are caused by positive-going inputs) or inverting (i.e., where positive output
transitions are caused by negative-going inputs).
The symbol for Schmitt triggers in circuit diagrams is a triangle with a symbol inside
representing its ideal hysteresis curve.
Transistor Schmitt triggers
Classic emitter-coupled circuit
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Schmitt trigger implemented by two emitter-coupled transistor stages
The original Schmitt trigger is based on the dynamic threshold idea that is implemented by a
voltage divider with a switchable upper leg (the collector resistors RC1 and RC2) and a steady
lower leg (RE). Q1 acts as a comparator with a differential input (Q1 base-emitter junction)
consisting of an inverting (Q1 base) and a non-inverting (Q1 emitter) inputs. The input
voltage is applied to the inverting input; the output voltage of the voltage divider is applied to
the non-inverting input thus determining its threshold. The comparator output drives the
second common collector stage Q2 (an emitter follower) through the voltage divider R1-R2.
The emitter-coupled transistors Q1 and Q2 actually compose an electronic double throw
switch that switches over the upper legs of the voltage divider and changes the threshold in a
different (to the input voltage) direction.
This configuration can be considered as a differential amplifier with series positive feedback
between its non-inverting input (Q2 base) and output (Q1 collector) that forces the transition
process. There is also a smaller negative feedback introduced by the emitter resistor R E. To
make the positive feedback dominate over the negative one and to obtain a hysteresis, the
proportion between the two collector resistors is chosen RC1 > RC2. Thus less current flows
through and less voltage drop is across RE when Q1 is switched on than in the case when Q2
is switched on. As a result, the circuit has two different thresholds in regard to ground (V- in
the picture).
Operation
Initial state. For NPN transistors as shown, imagine the input voltage is below the shared
emitter voltage (high threshold for concreteness) so that Q1 base-emitter junction is
DEPARTMENT OF ECS
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backward-biased and Q1 does not conduct. Q2 base voltage is determined by the mentioned
divider so that Q2 is conducting and the trigger output is in the low state. The two resistors
RC2 and RE form another voltage divider that determines the high threshold. Neglecting VBE,
the high threshold value is approximately
.
The output voltage is low but well above the ground. It is approximately equal to the high
threshold and may not be low enough to be a logical zero for next digital circuits. This may
require additional shifting circuit following the trigger circuit.
Crossing up the high threshold. When the input voltage (Q1 base voltage) rises slightly
above the voltage across the emitter resistor RE (the high threshold), Q1 begins conducting.
Its collector voltage goes down and Q2 begins going cut-off, because the voltage divider now
provides lower Q2 base voltage. The common emitter voltage follows this change and goes
down thus making Q1 conduct more. The current begins steering from the right leg of the
circuit to the left one. Although Q1 is more conducting, it passes less current through R E
(since RC1 > RC2); the emitter voltage continues dropping and the effective Q1 base-emitter
voltage continuously increases. This avalanche-like process continues until Q1 becomes
completely turned on (saturated) and Q2 turned off. The trigger is transitioned to the high
state and the output (Q2 collector) voltage is close to V+. Now, the two resistors R C1 and RE
form a voltage divider that determines the low threshold. Its value is approximately
.
Crossing down the low threshold. With the trigger now in the high state, if the input voltage
lowers enough (below the low threshold), Q1 begins cutting-off. Its collector current reduces;
as a result, the shared emitter voltage lowers slightly and Q1 collector voltage rises
significantly. R1-R2 voltage divider conveys this change to Q2 base voltage and it begins
conducting. The voltage across RE rises, further reducing the Q1 base-emitter potential in the
same avalanche-like manner, and Q1 ceases to conduct. Q2 becomes completely turned on
(saturated) and the output voltage becomes low again.
DEPARTMENT OF ECS
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Variations
Symbol depicting an inverting Schmitt trigger by showing an inverted hysteresis curve inside
a buffer. Other symbols show a hysteresis curve (which may be inverting or non-inverting)
embedded in a buffer followed by a bubble, which is similar to the traditional symbol for a
digital inverter that shows a buffer followed by a bubble. In general, the direction of the
Schmitt trigger (inverting or non-inverting) is not necessarily clear from the symbol because
multiple conventions are used, even with the same manufacturer. There are several factors
leading to such ambiguity,[nb 1] These circumstances may warrant a closer investigation of the
documentation for each particular Schmitt trigger.
Non-inverting circuit. The classic non-inverting Schmitt trigger can be turned into an
inverting trigger by taking Vout from the emitters instead of from a Q2 collector. In this
configuration, the output voltage is equal to the dynamic threshold (the shared emitter
voltage) and both the output levels stay away from the supply rails. Another disadvantage is
that the load changes the thresholds; so, it has to be high enough. The base resistor RB is
obligatory to prevent the impact of the input voltage through Q1 base-emitter junction on the
emitter voltage.
Direct-coupled circuit. To simplify the circuit, the R1–R2 voltage divider can be omitted
connecting Q1 collector directly to Q2 base. The base resistor RB can be omitted as well so
that the input voltage source drives directly Q1 base.[4] In this case, the common emitter
voltage and Q1 collector voltage are not suitable for outputs. Only Q2 collector should be
used as an output since, when the input voltage exceeds the high threshold and Q1 saturates,
its base-emitter junction is forward biased and transfers the input voltage variations directly
to the emitters. As a result, the common emitter voltage and Q1 collector voltage follow the
input voltage. This situation is typical for over-driven transistor differential amplifiers and
ECL gates.
DEPARTMENT OF ECS
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Collector-base coupled circuit
BJT bistable collector-base coupled circuit can be converted to a Schmitt trigger by
connecting an additional base resistor to one of the bases
Like every latch, the funkdamental collector-base coupled bistable circuit possesses a
hysteresis. So, it can be converted to a Schmitt trigger by connecting an additional base
resistor R to some of the inputs (Q1 base in the figure). The two resistors R and R4 form a
parallel voltage summer (the circle in the ballock diagram above) that sums output (Q2
collector) voltage and the input voltage, and drives the single-ended transistor "comparator"
Q1. When the base voltage crosses the threshold (VBE0 ∞ 0.65 V) in some direction, a part of
Q2 collector voltage is added in the same direction to the input voltage. Thus the output
modifies the input voltage by means of parallel positive feedback and does not affect the
threshold (the base-emitter voltage).
Comparison between emitter- and collector-coupled circuit
The emitter-coupled version has the advantage that the input transistor is backward-biased
when the input voltage is quite below the high threshold; so, the transistor is surely cut-off. It
was important when germanium transistors were used for implementing the circuit and this
advantage has determined its popularity. The input base resistor can be omitted since the
emitter resistor limits the current when the input base-emitter junction is forward-biased.
The emitter-coupled Schmitt trigger has not low enough level at output logical zero and
needs an additional output shifting circuit. The collector-coupled trigger has extremely low
(almost zero) output level at output logical zero.
Op-amp implementations
DEPARTMENT OF ECS
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Schmitt triggers are commonly implemented using an operational amplifier or the more
dedicated comparator.[nb 2] An open-loop op-amp and comparator may be considered as an
analog-digital device having analog inputs and a digital output that extracts the sign of the
voltage difference between its two inputs.[nb 3] The positive feedback is applied by adding a
part of the output voltage to the input voltage in series or parallel manner. Due to the
extremely high op-amp gain, the loop gain is also high enough and provides the avalanchelike process.
A rectifier is an electrical device that converts alternating current (AC), which periodically
reverses direction, to direct current (DC), which flows in only one direction. The process is
known as rectification. Physically, rectifiers take a number of forms, including vacuum tube
diodes, mercury-arc valves, copper and selenium oxide rectifiers, semiconductor diodes,
silicon-controlled rectifiers and other silicon-based semiconductor switches. Historically,
even synchronous electromechanical switches and motors have been used. Early radio
receivers, called crystal radios, used a "cat's whisker" of fine wire pressing on a crystal of
galena (lead sulfide) to serve as a point-contact rectifier or "crystal detector".
Rectifiers have many uses, but are often found serving as components of DC power supplies
and high-voltage direct current power transmission systems. Rectification may serve in roles
other than to generate direct current for use as a source of power. As noted, detectors of radio
signals serve as rectifiers. In gas heating systems flame rectification is used to detect presence
of a flame.
Because of the alternating nature of the input AC sine wave, the process of rectification alone
produces a DC current that, though unidirectional, consists of pulses of current. Many
applications of rectifiers, such as power supplies for radio, television and computer
equipment, require a steady constant DC current (as would be produced by a battery). In
these applications the output of the rectifier is smoothed by an electronic filter (usually a
capacitor) to produce a steady current.
A more complex circuitry device that performs the opposite function, converting DC to AC,
is called an inverter.
Rectifier devices
DEPARTMENT OF ECS
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Before the development of silicon semiconductor rectifiers, vacuum tube thermionic diodes
and copper oxide- or selenium-based metal rectifier stacks were used.[1] With the introduction
of semiconductor electronics, vacuum tube rectifiers became obsolete, except for some
enthusiasts of vacuum tube audio equipment. For power rectification from very low to very
high current, semiconductor diodes of various types (junction diodes, Schottky diodes, etc.)
are widely used.
Other devices that have control electrodes as well as acting as unidirectional current valves
are used where more than simple rectification is required—e.g., where variable output
voltage is needed. High-power rectifiers, such as those used in high-voltage direct current
power transmission, employ silicon semiconductor devices of various types. These are
thyristors or other controlled switching solid-state switches, which effectively function as
diodes to pass current in only one direction.
Linear half wave rectifiers:
Rectifier circuits may be single-phase or multi-phase (three being the most common number
of phases). Most low power rectifiers for domestic equipment are single-phase, but threephase rectification is very important for industrial applications and for the transmission of
energy as DC (HVDC).
Single-phase rectifiers
Half-wave rectification
In half wave rectification of a single-phase supply, either the positive or negative half of the
AC wave is passed, while the other half is blocked. Because only one half of the input
waveform reaches the output, mean voltage is lower. Half-wave rectification requires a single
diode in a single-phase supply, or three in a three-phase supply. Rectifiers yield a
unidirectional but pulsating direct current; half-wave rectifiers produce far more ripple than
full-wave rectifiers, and much more filtering is needed to eliminate harmonics of the AC
frequency from the output.
Precision rectifier
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Full-wave rectification
A full-wave rectifier converts the whole of the input waveform to one of constant polarity
(positive or negative) at its output. Full-wave rectification converts both polarities of the
input waveform to pulsating DC (direct current), and yields a higher average output voltage.
Two diodes and a center tapped transformer, or four diodes in a bridge configuration and any
AC source (including a transformer without center tap), are needed.[3] Single semiconductor
diodes, double diodes with common cathode or common anode, and four-diode bridges, are
manufactured as single components.
For single-phase AC, if the transformer is center-tapped, then two diodes back-to-back
(cathode-to-cathode or anode-to-anode, depending upon output polarity required) can form a
full-wave rectifier. Twice as many turns are required on the transformer secondary to obtain
the same output voltage than for a bridge rectifier, but the power rating is unchanged.
Full-wave rectifier using a center tap transformer and 2 diodes.
Full-wave rectifier, with vacuum tube having two anodes.
DEPARTMENT OF ECS
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The average and root-mean-square no-load output voltages of an ideal single-phase full-wave
rectifier are:
Very common double-diode rectifier vacuum tubes contained a single common cathode and
two anodes inside a single envelope, achieving full-wave rectification with positive output.
The 5U4 and 5Y3 were popular examples of this configuration.
Three-phase rectifiers
3-phase AC input, half and full-wave rectified DC output waveforms
Single-phase rectifiers are commonly used for power supplies for domestic equipment.
However, for most industrial and high-power applications, three-phase rectifier circuits are
the norm. As with single-phase rectifiers, three-phase rectifiers can take the form of a halfwave circuit, a full-wave circuit using a center-tapped transformer, or a full-wave bridge
circuit.
Thyristors are commonly used in place of diodes to create a circuit that can regulate the
output voltage. Many devices that provide direct current actually generate three-phase AC.
DEPARTMENT OF ECS
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For example, an automobile alternator contains six diodes, which function as a full-wave
rectifier for battery charging.
Three-phase, half-wave circuit
An uncontrolled three-phase, half-wave circuit requires three diodes, one connected to each
phase. This is the simplest type of three-phase rectifier but suffers from relatively high
harmonic distortion on both the AC and DC connections. This type of rectifier is said to have
a pulse-number of three, since the output voltage on the DC side contains three distinct
pulses per cycle of the grid frequency.
Three-phase, full-wave circuit using center-tapped transformer
If the AC supply is fed via a transformer with a center tap, a rectifier circuit with improved
harmonic performance can be obtained. This rectifier now requires six diodes, one connected
to each end of each transformer secondary winding. This circuit has a pulse-number of six,
and in effect, can be thought of as a six-phase, half-wave circuit.
Before solid state devices became available, the half-wave circuit, and the full-wave circuit
using a center-tapped transformer, were very commonly used in industrial rectifiers using
mercury-arc valves.[4] This was because the three or six AC supply inputs could be fed to a
corresponding number of anode electrodes on a single tank, sharing a common cathode.
With the advent of diodes and thyristors, these circuits have become less popular and the
three-phase bridge circuit has become the most common circuit.
Three-phase half-wave rectifier circuit using thyristors as the switching elements, ignoring
DEPARTMENT OF ECS
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supply inductance.
PEAK DETECTOR
Peak Detector is a type of electronic detector or rectifier. Quasi-peak detectors for specific
purposes have usually been standardized with mathematically precisely defined dynamic
characteristics of attack time, integration time, and decay time or fall-back time.
peak detectors play an important role in electromagnetic compatibility (EMC) testing of
electronic equipment, where allowed levels of electromagnetic interference (EMI), also called
radio frequency interference (RFI), are given with reference to measurement by a specified
quasi-peak detector. This was originally done because the quasi-peak detector was believed
to better indicate the subjective annoyance level experienced by a listener hearing impulsive
interference to an AM radio station. Over time standards incorporating quasi-peak detectors
as the measurement device were extended to frequencies up to 1 GHz, although there may not
be any justification beyond previous practice for using the quasi-peak detector to measure
interference to signals other than AM radio. The quasi-peak detector parameters to be used
for EMC testing vary with frequency . Both CISPR and the U.S. Federal Communications
Commission (FCC) limit EMI at frequencies above 1 GHz with reference to an averagepower detector, rather than quasi-peak detector.
Conceptually, a quasi-peak detector for EMC testing works like a peak detector followed by a
lossy integrator. A voltage impulse entering a narrow-band receiver produces a short-duration
burst oscillating at the receiver center frequency. The peak detector is a rectifier followed by
a low-pass filter to extract a baseband signal consisting of the slowly (relative to the receiver
center frequency) time-varying amplitude of the impulsive oscillation. The following lossy
integrator has a rapid rise time and longer fall time, so the measured output for a sequence of
impulses is higher when the pulse repetition rate is higher. The quasi-peak detector is
calibrated to produce the same output level as a peak-power detector when the input is a
continuous wave tone .
Sample and hold
.
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A simplified sample and hold circuit diagram. AI is an analog input, AO — an analog output,
C — a control signal.
Sample times.
Sample and hold.
A typical sample and hold circuit stores electric charge in a capacitor and contains at least
one fast FET (field effect transistor) switch and at least one operational amplifier.[1] To
sample the input signal the switch connects the capacitor to the output of a buffer amplifier.
The buffer amplifier charges or discharges the capacitor so that the voltage across the
capacitor is practically equal, or proportional to, input voltage. In hold mode the switch
disconnects the capacitor from the buffer. The capacitor is invariably discharged by its own
leakage currents and useful load currents, which makes the circuit inherently volatile, but the
loss of voltage (voltage drop) within a specified hold time remains within an acceptable error
margin.
Purpose
Sample and hold circuits are used in linear systems. In some kinds of analog-to-digital
converters, the input is compared to a voltage generated internally from a digital-to-analog
converter (DAC). The circuit tries a series of values and stops converting once the voltages
are equal, within some defined error margin. If the input value was permitted to change
DEPARTMENT OF ECS
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during this comparison process, the resulting conversion would be inaccurate and possibly
completely unrelated to the true input value. Such successive approximation converters will
often incorporate internal sample and hold circuitry. In addition, sample and hold circuits are
often used when multiple samples need to be measured at the same time. Each value is
sampled and held, using a common sample clock.
For practically all commercial liquid crystal active matrix displays based on TN, IPS or
VA electro-optic LC cells (excluding bi-stable phenomena), each pixel represents a small
capacitor, which has to be periodically charged to a level corresponding to the greyscale
value (contrast) desired for a picture element. In order to maintain the level during a scanning
cycle (frame period), an additional electric capacitor is attached in parallel to each LC pixel
to better hold the voltage.
Clipper and clampers
Voltage clipping limits the voltage to a device without affecting the rest of the waveform
In electronics, a clipper is a device designed to prevent the output of a circuit from exceeding
a predetermined voltage level without distorting the remaining part of the applied waveform.
A clipping circuit consists of linear elements like resistors and non-linear elements like
junction diodes or transistors, but it does not contain energy-storage elements like capacitors.
Clipping circuits are used to select for purposes of transmission, that part of a signal wave
form which lies above or below a certain reference voltage level.
Thus a clipper circuit can remove certain portions of an arbitrary waveform near the positive
or negative peaks. Clipping may be achieved either at one level or two levels. Usually under
the section of clipping, there is a change brought about in the wave shape of the signal.
Clipping circuits are also called slicers, amplitude selectors or limiters.
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Types
Diode clipper
Positive peak clipper circuit
A simple diode clipper can be made with a diode and a resistor. This will remove either the
positive, or the negative half of the waveform depending on the direction the diode is
connected. The simple circuit clips at zero voltage (or to be more precise, at the small
forward voltage of the forward biased diode) but the clipping voltage can be set to any
desired value with the addition of a reference voltage. The diagram illustrates a positive
reference voltage but the reference can be positive or negative for both positive and negative
clipping giving four possible configurations in all.
The simplest circuit for the voltage reference is a resistor potential divider connected between
the voltage rails. This can be improved by replacing the lower resistor with a zener diode
with a breakdown voltage equal to the required reference voltage. The zener acts as a voltage
regulator stabilising the reference voltage against supply and load variations.
Zener diode
Two shunt diode clipper circuits
In the example circuits above, two zener diodes are used to clip the voltage VIN. The voltage
in either direction is limited to the reverse breakdown voltage plus the voltage drop across
one zener diode.
Op-amp precision clipper
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For very small values of clipping voltage on low-level signals the I-V curve of the diode can
result in clipping onset that is not very sharp. Precision clippers can be made by placing the
clipping device in the feedback circuit of an operational amplifier in a similar way to
precision rectifiers.
Classification
Clippers may be classified into two types based on the positioning of the diode. [1]

Series Clippers, where the diode is in series with the load resistance, and

Shunt Clippers, where the diode is shunted across the load resistance.
The diode capacitance affects the operation of the clipper at high frequency and influences
the choice between the above two types. High frequency signals are attenuated in the shunt
clipper as the diode capacitance provides an alternative path to output current. In the series
clipper, clipping effectiveness is reduced for the same reason as the high frequency current
passes through without being sufficiently blocked.
Clippers may be classified based on the orientation(s) of the diode. The orientation decides
which half cycle is affected by the clipping action.
The clipping action can be made to happen at an arbitrary level by using a biasing elements
(potential sources) in series with the diode.

Positively Biased Diode Clipper

Negatively Biased Diode Clipper
The signal can be clipped to between two levels by using both types of diode clippers in
combination. This clipper is referred to as

Combinational Diode Clipper or Two-Level Clippers
The clamping network is the one that will "clamp" a signal to a different dc level. The
network must have capacitor, a diode, and a resistive element, but it also employs an
independent dc supply to introduce an additional shift.
Butterworth filter
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The frequency response plot from Butterworth's 1930 paper.[1]
The Butterworth filter is a type of signal processing filter designed to have as flat a
frequency response as possible in the passband. It is also referred to as a maximally flat
magnitude filter.
"An ideal electrical filter should not only completely reject the unwanted frequencies but
should also have uniform sensitivity for the wanted frequencies".
Such an ideal filter cannot be achieved but Butterworth showed that successively closer
approximations were obtained with increasing numbers of filter elements of the right values.
At the time, filters generated substantial ripple in the passband, and the choice of component
values was highly interactive. Butterworth showed that a low pass filter could be designed
whose cutoff frequency was normalized to 1 radian per second and whose frequency response
(gain) was
where ω is the angular frequency in radians per second and n is the number of poles in the
filter—equal to the number of reactive elements in a passive filter. If ω = 1, the amplitude
response of this type of filter in the passband is 1/√2 ≈ 0.707, which is half power or −3 dB.
Butterworth only dealt with filters with an even number of poles in his paper. He may have
been unaware that such filters could be designed with an odd number of poles. He built his
higher order filters from 2-pole filters separated by vacuum tube amplifiers. His plot of the
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frequency response of 2, 4, 6, 8, and 10 pole filters is shown as A, B, C, D, and E in his
original graph.
Butterworth solved the equations for two- and four-pole filters, showing how the latter could
be cascaded when separated by vacuum tube amplifiers and so enabling the construction of
higher-order filters despite inductor losses. In 1930, low-loss core materials such as
molypermalloy had not been discovered and air-cored audio inductors were rather lossy.
Butterworth discovered that it was possible to adjust the component values of the filter to
compensate for the winding resistance of the inductors.
Butterworth also showed that his basic low-pass filter could be modified to give low-pass,
high-pass, band-pass and band-stop functionality.
Overview
The Bode plot of a first-order Butterworth low-pass filter
The frequency response of the Butterworth filter is maximally flat (i.e. has no ripples) in the
passband and rolls off towards zero in the stopband.[2] When viewed on a logarithmic Bode
plot, the response slopes off linearly towards negative infinity. A first-order filter's response
rolls off at −6 dB per octave (−20 dB per decade) (all first-order lowpass filters have the same
normalized frequency response). A second-order filter decreases at −12 dB per octave, a
third-order at −18 dB and so on. Butterworth filters have a monotonically changing
magnitude function with ω, unlike other filter types that have non-monotonic ripple in the
passband and/or the stopband.
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Compared with a Chebyshev Type I/Type II filter or an elliptic filter, the Butterworth filter
has a slower roll-off, and thus will require a higher order to implement a particular stopband
specification, but Butterworth filters have a more linear phase response in the pass-band than
Chebyshev Type I/Type II and elliptic filters can achieve.
Example
A third-order low-pass filter (Cauer topology). The filter becomes a Butterworth filter with
cutoff frequency ωc=1 when (for example) C2=4/3 farad, R4=1 ohm, L1=3/2 henry and L3=1/2
henry.
A simple example of a Butterworth filter is the third-order low-pass design shown in the
figure on the right, with C2 = 4/3 F, R4 = 1 Ω, L1 = 3/2 H, and L3 = 1/2 H.[3] Taking the
impedance of the capacitors C to be 1/(Cs) and the impedance of the inductors L to be Ls,
where s = σ + jω is the complex frequency, the circuit equations yield the transfer function
for this device:
The magnitude of the frequency response (gain) G(ω) is given by
obtained from
and the phase is given by
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Gain and group delay of the third-order Butterworth filter with ωc=1
The group delay is defined as the derivative of the phase with respect to angular frequency
and is a measure of the distortion in the signal introduced by phase differences for different
frequencies. The gain and the delay for this filter are plotted in the graph on the left. It can be
seen that there are no ripples in the gain curve in either the passband or the stop band.
The log of the absolute value of the transfer function H(s) is plotted in complex frequency
space in the second graph on the right. The function is defined by the three poles in the left
half of the complex frequency plane.
Band-pass filter
Bandwidth measured at half-power points (gain -3 dB, √2/2, or about 0.707 relative to peak)
on a diagram showing magnitude transfer function versus frequency for a band-pass filter.
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A medium-complexity example of a band-pass filter.
A band-pass filter is a device that passes frequencies within a certain range and rejects
(attenuates) frequencies outside that range.
Bandpass is an adjective that describes a type of filter or filtering process; it is to be
distinguished from passband, which refers to the actual portion of affected spectrum. Hence,
one might say "A dual bandpass filter has two passbands." A bandpass signal is a signal
containing a band of frequencies not adjacent to zero frequency, such as a signal that comes
out of a bandpass filter.[2]
An ideal bandpass filter would have a completely flat passband (e.g. with no gain/attenuation
throughout) and would completely attenuate all frequencies outside the passband.
Additionally, the transition out of the passband would have brickwall characteristics.
In practice, no bandpass filter is ideal. The filter does not attenuate all frequencies outside the
desired frequency range completely; in particular, there is a region just outside the intended
passband where frequencies are attenuated, but not rejected. This is known as the filter rolloff, and it is usually expressed in dB of attenuation per octave or decade of frequency.
Generally, the design of a filter seeks to make the roll-off as narrow as possible, thus
allowing the filter to perform as close as possible to its intended design. Often, this is
achieved at the expense of pass-band or stop-band ripple.
The bandwidth of the filter is simply the difference between the upper and lower cutoff
frequencies. The shape factor is the ratio of bandwidths measured using two different
attenuation values to determine the cutoff frequency, e.g., a shape factor of 2:1 at 30/3 dB
means the bandwidth measured between frequencies at 30 dB attenuation is twice that
measured between frequencies at 3 dB attenuation.
Optical band-pass filters are common in photography and theatre lighting work. These filters
take the form of a transparent coloured film or sheet.
Q factor
A band-pass filter can be characterised by its Q factor. The Q-factor is the inverse of the
fractional bandwidth. A high-Q filter will have a narrow passband and a low-Q filter will
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have a wide passband. These are respectively referred to as narrow-band and wide-band
filters.
Applications
Bandpass filters are widely used in wireless transmitters and receivers. The main function of
such a filter in a transmitter is to limit the bandwidth of the output signal to the band allocated
for the transmission. This prevents the transmitter from interfering with other stations. In a
receiver, a bandpass filter allows signals within a selected range of frequencies to be heard or
decoded, while preventing signals at unwanted frequencies from getting through. A bandpass
filter also optimizes the signal-to-noise ratio and sensitivity of a receiver.
In both transmitting and receiving applications, well-designed bandpass filters, having the
optimum bandwidth for the mode and speed of communication being used, maximize the
number of signal transmitters that can exist in a system, while minimizing the interference or
competition among signals.
Band-stop filter
A generic ideal band-stop filter, showing both positive and negative angular frequencies
In signal processing, a band-stop filter or band-rejection filter is a filter that passes most
frequencies unaltered, but attenuates those in a specific range to very low levels. It is the
opposite of a band-pass filter. A notch filter is a band-stop filter with a narrow stopband
(high Q factor).
Narrow notch filters (optical) are used in Raman spectroscopy, live sound reproduction
(public address systems, or PA systems) and in instrument amplifiers (especially amplifiers
or preamplifiers for acoustic instruments such as acoustic guitar, mandolin, bass instrument
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amplifier, etc.) to reduce or prevent audio feedback, while having little noticeable effect on
the rest of the frequency spectrum (electronic or software filters). Other names include 'band
limit filter', 'T-notch filter', 'band-elimination filter', and 'band-reject filter'.
Typically, the width of the stopband is 1 to 2 decades (that is, the highest frequency
attenuated is 10 to 100 times the lowest frequency attenuated). However, in the audio band, a
notch filter has high and low frequencies that may be only semitones apart.
Generic electrical schematic of a simple band-stop filter
Low-pass filter
A low-pass filter is a filter that passes signals with a frequency lower than a certain cutoff
frequency and attenuates signals with frequencies higher than the cutoff frequency. The
amount of attenuation for each frequency depends on the filter design. The filter is sometimes
called a high-cut filter, or treble cut filter in audio applications. A low-pass filter is the
opposite of a high-pass filter. A band-pass filter is a combination of a low-pass and a highpass filter.
Low-pass filters exist in many different forms, including electronic circuits (such as a hiss
filter used in audio), anti-aliasing filters for conditioning signals prior to analog-to-digital
conversion, digital filters for smoothing sets of data, acoustic barriers, blurring of images, and
so on. The moving average operation used in fields such as finance is a particular kind of
low-pass filter, and can be analyzed with the same signal processing techniques as are used
for other low-pass filters. Low-pass filters provide a smoother form of a signal, removing the
short-term fluctuations, and leaving the longer-term trend.
An optical filter can correctly be called a low-pass filter, but conventionally is called a
longpass filter (low frequency is long wavelength), to avoid confusion.
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Continuous-time low-pass filters
The gain-magnitude frequency response of a first-order (one-pole) low-pass filter. Power
gain is shown in decibels (i.e., a 3 dB decline reflects an additional half-power attenuation).
Angular frequency is shown on a logarithmic scale in units of radians per second.
There are many different types of filter circuits, with different responses to changing
frequency. The frequency response of a filter is generally represented using a Bode plot, and
the filter is characterized by its cutoff frequency and rate of frequency rolloff. In all cases, at
the cutoff frequency, the filter attenuates the input power by half or 3 dB. So the order of the
filter determines the amount of additional attenuation for frequencies higher than the cutoff
frequency.

A first-order filter, for example, reduces the signal amplitude by half (so power
reduces by a factor of 4, or 6 dB), every time the frequency doubles (goes up one
octave); more precisely, the power rolloff approaches 20 dB per decade in the limit of
high frequency. The magnitude Bode plot for a first-order filter looks like a horizontal
line below the cutoff frequency, and a diagonal line above the cutoff frequency. There
is also a "knee curve" at the boundary between the two, which smoothly transitions
between the two straight line regions. If the transfer function of a first-order low-pass
filter has a zero as well as a pole, the Bode plot flattens out again, at some maximum
attenuation of high frequencies; such an effect is caused for example by a little bit of
the input leaking around the one-pole filter; this one-pole–one-zero filter is still a
first-order low-pass. See Pole–zero plot and RC circuit.

A second-order filter attenuates higher frequencies more steeply. The Bode plot for
this type of filter resembles that of a first-order filter, except that it falls off more
quickly. For example, a second-order Butterworth filter reduces the signal amplitude
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to one fourth its original level every time the frequency doubles (so power decreases
by 12 dB per octave, or 40 dB per decade). Other all-pole second-order filters may
roll off at different rates initially depending on their Q factor, but approach the same
final rate of 12 dB per octave; as with the first-order filters, zeroes in the transfer
function can change the high-frequency asymptote. See RLC circuit.

Third- and higher-order filters are defined similarly. In general, the final rate of power
rolloff for an order-
all-pole filter is
dB per octave (i.e.,
dB per decade).
High pass filter

A high-pass filter is an electronic filter that passes signals with a frequency higher
than a certain cutoff frequency and attenuates signals with frequencies lower than the
cutoff frequency. The amount of attenuation for each frequency depends on the filter
design. A high-pass filter is usually modeled as a linear time-invariant system. It is
sometimes called a low-cut filter or bass-cut filter.[1] High-pass filters have many
uses, such as blocking DC from circuitry sensitive to non-zero average voltages or
radio frequency devices. They can also be used in conjunction with a low-pass filter
to produce a bandpass filter.

First-order continuous-time implementation


Figure 1: A passive, analog, first-order high-pass filter, realized by an RC circuit

The simple first-order electronic high-pass filter shown in Figure 1 is implemented by
placing an input voltage across the series combination of a capacitor and a resistor and
using the voltage across the resistor as an output. The product of the resistance and
capacitance (R×C) is the time constant (τ); it is inversely proportional to the cutoff
frequency fc, that is,


where fc is in hertz, τ is in seconds, R is in ohms, and C is in farads.
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

Figure 2: An active high-pass filter

Figure 2 shows an active electronic implementation of a first-order high-pass filter
using an operational amplifier. In this case, the filter has a passband gain of -R2/R1
and has a cutoff frequency of


Because this filter is active, it may have non-unity passband gain. That is, highfrequency signals are inverted and amplified by R2/R1.

Discrete-time realization

For another method of conversion from continuous- to discrete-time, see Bilinear
transform.

Discrete-time high-pass filters can also be designed. Discrete-time filter design is
beyond the scope of this article; however, a simple example comes from the
conversion of the continuous-time high-pass filter above to a discrete-time realization.
That is, the continuous-time behavior can be discretized.

From the circuit in Figure 1 above, according to Kirchhoff's Laws and the definition
of capacitance:


where
is the charge stored in the capacitor at time . Substituting Equation (Q)
into Equation (I) and then Equation (I) into Equation (V) gives:


This equation can be discretized. For simplicity, assume that samples of the input and
output are taken at evenly-spaced points in time separated by
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time. Let the
samples of
be represented by the sequence
represented by the sequence
, and let
be
which correspond to the same points
in time. Making these substitutions:


And rearranging terms gives the recurrence relation


That is, this discrete-time implementation of a simple continuous-time RC high-pass
filter is


By definition,
. The expression for parameter
time constant
in terms of the sampling period


:
.
Recalling that


and
yields the equivalent
so
then
and
are related by:


and


.
If
then
, then the
time constant equal to the sampling period. If
is significantly smaller than the sampling interval, and
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,
.
POINTS TO REMEMBER:

A comparator consists of a specialized high-gain differential amplifier. They are
commonly used in devices that measure and digitize analog signals, such as analogto-digital converters (ADCs), as well as relaxation oscillators.

Op-amps are designed to operate in the linear mode with negative feedback. Hence,
an op-amp typically has a lengthy recovery time from saturation.

All op-amps have an internal compensation capacitor which imposes slew rate
limitations for high frequency signals. Consequently an op-amp makes a sloppy
comparator with propagation delays that can be as long as tens of microseconds.

Since op-amps do not have any internal hysteresis, an external hysteresis network is
always necessary for slow moving input signals.

The quiescent current specification of an op-amp is valid only when the feedback is
active.

Some op-amps show an increased quiescent current when the inputs are not equal.

A comparator is designed to produce well limited output voltages that easily interface
with digital logic.

Compatibility with digital logic must be verified while using an op-amp as a
comparator.

Some multiple-section op-amps may exhibit extreme channel-channel interaction
when used as comparators.

Many op-amps have back to back diodes between their inputs. Op-amp inputs usually
follow each other so this is fine. But comparator inputs are not usually the same.

The diodes can cause unexpected current through inputs.
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Expected Questions:
1. Explain with neat diagram of Schmitt Triggers.
2. Illustrate the function of the sample and hold circuits.
3. Explain the function of clippers and clampers.
4. Explain the types of filters with a neat diagram.
5. Explain the function of peak detectors.
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