Data Sheet
High Voltage, 1.2 MHz/600 kHz, 800 mA,
Low Quiescent Current Buck Regulator
ADP2370/ADP2371
FEATURES
TYPICAL APPLICATION CIRCUIT
VIN = 6V
CIN
10µF
POWER GOOD
VIN
1.2MHz
600kHz
ON
ADP2370/
ADP2371
1
8
FSEL 2
7
EN
3
OFF
6
PGND
SW
PG
VOUT = 3.3V
COUT
10µF
AGND
(EXPOSED PAD)
SYNC
4
5
FB
09531-001
Input voltage range: 3.2 V to 15 V, output current: 800 mA
Quiescent current < 14 μA in power saving mode (PSM)
>90% efficiency
Force PWM pin (SYNC), 600 kHz/1.2 MHz frequency pin
(FSEL)
Fixed outputs: 0.8 V, 1.2 V, 1.5 V, 1.8 V, 2.5 V, 3.0 V, 3.3 V, 5 V,
and adjustable option
100% duty cycle capability
Initial accuracy: ±1%
Low shutdown current: <1.2 μA
Quick output discharge (QOD) option
Synchronizable to an external clock
8-lead, 0.75 mm × 3 mm × 3 mm LFCSP (QFN) package
Supported by ADIsimPower design tool
Figure 1.
APPLICATIONS
Portable and battery-powered equipment
Automatic meter readers (WSN)
Point of sales and transaction processing instruments
Medical instruments
Medium format display tablets and pads
GENERAL DESCRIPTION
The ADP2370/ADP2371 are high efficiency, low quiescent current,
800 mA buck (step-down) dc-to-dc converters in small 8-lead,
3 mm × 3 mm LFCSP (QFN) packages. The total solution requires
only three tiny external components.
The buck regulator uses a proprietary high speed current mode,
constant frequency PWM control scheme for excellent stability
and transient response. The need for an external rectifier is eliminated by using a high efficiency synchronous rectifier architecture.
To ensure the longest battery life in portable applications, the
ADP2370/ADP2371 employ a power saving variable frequency
mode that reduces the switching frequency under light load
conditions. The ADP2370/ADP2371 operate from input voltages
of 3.2 V to 15 V allowing the use of multiple alkaline/NiMH,
lithium cells, or other standard power sources.
The ADP2370/ADP2371 offer multiple options for setting the
operational frequency. The ADP2370/ADP2371 can be synchronized to a 600 kHz to 1.2 MHz external clock or it can be forced
to operate at 600 kHz or 1.2 MHz via the FSEL pin. The ADP2370/
ADP2371 can be forced to operate in PWM mode (FPWM) when
noise considerations are more important than efficiency.
Rev. D
A power-good output is available to indicate when the output
voltage is below 92% of its nominal value.
The ADP2371 is identical to the ADP2370 except that the
ADP2371 includes the addition of an integrated switched
resistor, quick output discharge function (QOD) that automatically discharges the output when the device is disabled.
Both devices include an internal power switch and a synchronous
rectifier for minimal external part count and high efficiency.
The ADP2370/ADP2371 also include internal soft start and
internal compensation for ease of use.
During a logic controlled shutdown, the input is disconnected
from the output and the regulator draws less than 1.2 μA from
the input source. Other key features include undervoltage lockout
to prevent deep battery discharge and soft start to prevent input
overcurrent at startup. Short-circuit protection and thermal overload protection circuits prevent damage under adverse conditions.
The ADP2370/ADP2371 each use one 0805 capacitor, one 1206
capacitor, and one 4 mm × 4 mm inductor. The total solution
size is about 53 mm2 resulting in a very small footprint solution
to meet a variety of portable applications.
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ADP2370/ADP2371
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Undervoltage Lockout ............................................................... 22
Applications ....................................................................................... 1
Thermal Protection .................................................................... 22
Typical Application Circuit ............................................................. 1
Soft Start ...................................................................................... 22
General Description ......................................................................... 1
Current Limit .............................................................................. 22
Revision History ............................................................................... 2
100% Duty Cycle ........................................................................ 23
Specifications..................................................................................... 3
Synchronizing ............................................................................. 23
Recommended Specifications: Capacitors ................................ 5
Power Good ................................................................................ 24
Absolute Maximum Ratings ....................................................... 6
Applications Information .............................................................. 25
Thermal Data ................................................................................ 6
ADIsimPower Design Tool ....................................................... 25
Thermal Resistance ...................................................................... 6
External Component Selection ................................................ 25
ESD Caution .................................................................................. 6
Selecting the Inductor ................................................................ 25
Pin Configuration and Function Descriptions ............................. 7
Output Capacitor........................................................................ 25
Typical Performance Characteristics ............................................. 8
Input Capacitor ........................................................................... 25
Buck Output .................................................................................. 8
Adjustable Output Voltage Programming .............................. 25
Theory of Operation ...................................................................... 20
Efficiency ..................................................................................... 26
PWM Operation ......................................................................... 20
Recommended Buck External Components .......................... 26
PSM Operation ........................................................................... 21
Capacitor Selection .................................................................... 28
Features Descriptions ..................................................................... 22
Thermal Considerations ................................................................ 29
Precision Enable ......................................................................... 22
PCB Layout Considerations ...................................................... 30
Forced PWM or PWM/PSM Selection.................................... 22
Packaging and Ordering Information ......................................... 32
Quick Output Discharge (QOD) Function ............................. 22
Outline Dimensions ................................................................... 32
Short-Circuit Protection ............................................................ 22
Ordering Guide .......................................................................... 32
REVISION HISTORY
2/14—Rev. C to Rev. D
Change to Figure 13 ......................................................................... 9
Updated Outline Dimensions ....................................................... 32
11/12—Rev. B to Rev. C
Change to Figure 6 ........................................................................... 8
Changes to Ordering Guide............................................................. 32
8/12—Rev. A to Rev. B
Change to Figure 62 ....................................................................... 17
Changes to Figure 63, Figure 64, Figure 65, and Figure 66 ............ 18
5/12—Rev. 0 to Rev. A
Changed Voltage Range for SW to PGND and Ground Plane
from −0.3 V to VIN + 0.3 V to −0.7 V to VIN + 0.3 V ............... 6
Changes to Ordering Guide .......................................................... 32
4/12—Revision 0: Initial Version
Rev. D | Page 2 of 32
Data Sheet
ADP2370/ADP2371
SPECIFICATIONS
VIN = VOUT + 1 V or 3.2 V, whichever is greater, EN = VIN, IOUT = 100 mA, CIN = 10 μF, COUT = 10 µF, TA = 25°C for typical specifications,
TJ = −40°C to +125°C for minimum/maximum specifications, unless otherwise noted.
Table 1.
Parameter
SUPPLY
Input Voltage Range
Quiescent Current
Symbol
VIN
IQ-PSM
IQ-PWM
Shutdown Current
FIXED OUTPUT
Output Current
Fixed Output Accuracy
ADJUSTABLE OUTPUT
Feedback Voltage
Feedback Voltage Accuracy
Output Voltage Range
FIXED AND ADJUSTABLE OUTPUT
Load Regulation
Line Regulation
Efficiency
Overcurrent Frequency Foldback Threshold
Rising
Falling
PSM Threshold
Feedback Pin Input Current
Fixed
Adjustable
Minimum On Time
Soft Start Time
Active Pull-Down Resistance
(ADP2371)
POWER SWITCH
P-Channel On Resistance
N-Channel On Resistance
Current Limit
P-Channel
N-Channel
Leakage Current
P-Channel
N-Channel
ISW-PWM
ISHUT
IOUT
VOUT
Test Conditions/Comments
Min
Typ
Max
Unit
15
13.5
V
μA
725
μA
3.2
FSEL = VIN, SYNC = 0 V, no load, device not
switching
FSEL = VIN, SYNC = VIN, no load, device not
switching
FSEL = VIN, SYNC = VIN, no load, device switching
EN = GND, TJ = −40°C to +85°C
5.7
1.2
3.5
mA
μA
+1
+1.5
+3
mA
%
%
%
+1
14
V
%
V
Initial set point, IOUT = 250 mA, TJ = 25°C
IOUT = 250 mA
No load to full load, PWM mode
800
−1
−1.5
−3
VFB
VFB-TOL
VOUT-ADJ
Initial set point, IOUT = 250 mA, TJ = 25°C
No load to full load
−1
0.8
∆VOUT/∆IOUT
∆VOUT/∆VIN
EFF
No load to full load
IOUT = 250 mA
IOUT = 250 mA, VIN = 7.2 V, VOUT = 3.3 V
0.125
0.01
92
%/A
%/V
%
OCFOLDBACK-RISE
OCFOLDBACK-FALL
PSMTHRESHOLD
% of VOUT, VOUT rising
% of VOUT, VOUT falling
VIN = 7.2 V, VOUT = 3.3 V
50
37.5
170
%
%
mA
IFB-FIXED
IFB-ADJUST
ON-TIMEMIN
Fixed output voltage model
Adjustable output voltage model
VIN < 5.5 V
VIN > 5.5 V
When EN rises from 0 V to VIN, and VOUT = 0.9 × VOUT
2.5
10
65
40
350
260
μA
nA
ns
ns
μs
Ω
SSTIME
RPULL-DOWN
RDSON-P
RDSON-N
ILIM-P
ILIM-N
ILEAK-SW
0.8
100
60
400
VIN > 5.5 V, IOUT = 400 mA
VIN < 5.5 V, IOUT = 400 mA
VIN > 5.5 V, IOUT = 400 mA
VIN < 5.5 V, IOUT = 400 mA
400
500
280
400
Peak inductor current
Peak inductor current
1200
500
1300
550
mA
mA
0.01
0.01
1
1
μA
μA
Rev. D | Page 3 of 32
mΩ
mΩ
mΩ
mΩ
ADP2370/ADP2371
Parameter
OSCILLATOR
Oscillator Frequency
Data Sheet
Symbol
Test Conditions/Comments
Min
Typ
Max
Unit
fOSC
FSEL = VIN, 3.2 V ≤ VIN ≤ 15 V
FSEL = 0 V, 3.2 V ≤ VIN ≤ 15 V
FSEL = 0 V, 3.2 V ≤ VIN ≤ 15 V
FSEL = VIN, 3.2 V ≤ VIN ≤ 15 V
1.0
500
400
0.8
1.2
600
1.4
700
800
1.6
MHz
kHz
kHz
MHz
3.2 V ≤ VIN ≤ 15 V
3.2 V ≤ VIN ≤ 15 V
3.2 V ≤ VIN ≤ 15 V
VIN (1.2 MHz), 3.2 V ≤ VIN ≤ 5 V, FSEL = VIN
VIN (1.2 MHz), 5 V ≤ VIN ≤ 15 V, FSEL = VIN
SYNC = 0 V or SYNC = VIN
3.2 V ≤ VIN ≤ 15 V
1.2
Frequency Synchronization Range
fSYNC_RANGE
Synchronization Threshold
High
Low
Hysteresis
Typical Sync Duty Cycle Range
SYNCHIGH
SYNCLOW
SYNCHYS
SYNCDUTY
SYNC Pin Leakage Current
FSEL Threshold
High
Low
Hysteresis
FSEL Pin Leakage Current
POWER GOOD (PG PIN)
PG Threshold
Rising
Falling
Hysteresis
PG Output Low
PG Delay
Rising
Falling
PG Leakage
UNDERVOLTAGE LOCKOUT (UVLO)
Input Voltage Rising
Input Voltage Falling
Hysteresis
ENABLE INPUT STANDBY (EN PIN)
EN Input Logic
High
Low
Hysteresis
ENABLE INPUT PRECISION (EN PIN)
EN Input Logic
High
Low
Hysteresis
EN Input Leakage Current
EN Input Delay Time
THERMAL SHUTDOWN
Thermal Shutdown Threshold
Thermal Shutdown Hysteresis
SYNCLKG
FESLHIGH
FSELLOW
FSELHYS
FSELLKG
0.4
200
20
20
0.05
55
70
1
1
0.4
125
0.04
FSEL = 0 V or FSEL = VIN
1
V
V
mV
%
%
μA
V
V
mV
μA
3.2 V ≤ VIN ≤ 15 V
PGRISE
PGFALL
PGHYS
PGLOW
PGDELAYRISE
PGDELAYFALL
82.5
92
87
5
Pull-up current < 1 mA
0.3
VOUT crossing PG rising threshold, pull-up
current < 1 mA
VOUT crossing PG falling threshold, pull-up
current < 1 mA
PGLKG
%
%
%
V
20
μs
0.5
μs
0.04
UVLORISE
UVLOFALL
UVLOHYS
95
1
μA
3.19
V
V
mV
2.80
190
3.2 V ≤ VIN ≤ 15 V
V
ENSTBY-HIGH
ENSTBY-LOW
ENSTBY-HYS
1
0.4
V
mV
1.26
1.155
V
V
mV
µA
μs
125
3.2 V ≤ VIN ≤ 15 V
ENHIGH
ENLOW
ENHYS
IEN-LKG
TIEN-DLY
TSSD
TSSD-HYS
1.135
1.045
EN = VIN or GND
For VOUT = 0 V to 0.1 × VOUT when EN rises from
0 V to VIN
3.2 V ≤ VIN ≤ 15 V
TJ rising
Rev. D | Page 4 of 32
1.2
1.1
100
0.05
70
150
15
1
°C
°C
Data Sheet
ADP2370/ADP2371
RECOMMENDED SPECIFICATIONS: CAPACITORS
Table 2.
Parameter
MINIMUM INPUT and OUTPUT CAPACITANCE 1
CAPACITOR ESR
1
Symbol
CMIN
RESR
Test Conditions/Comments
TA = −40°C to +125°C
TA = −40°C to +125°C
Min
6.5
1
Typ
10
Max
10
Unit
µF
mΩ
The minimum input and output capacitance should be greater than 7 μF over the full range of operating conditions. The full range of operating conditions in the
application must be considered during device selection to ensure that the minimum capacitance specification is met. X7R- and X5R-type capacitors are recommended;
Y5V and Z5U capacitors are not recommended for use with any buck.
Rev. D | Page 5 of 32
ADP2370/ADP2371
Data Sheet
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter
VIN to PGND and Ground Plane
SW to PGND and Ground Plane
FB to PGND and Ground Plane
EN to PGND and Ground Plane
PG to PGND and Ground Plane
SYNC to PGND and Ground Plane
FSEL to PGND and Ground Plane
Temperature Range
Storage
Operating Ambient
Operating Junction
Soldering Conditions
Rating
−0.3 V to +17 V
−0.7 V to VIN + 0.3 V
−0.3 V to +6 V
−0.3 V to +17 V
−0.3 V to +17 V
−0.3 V to +17 V
−0.3 V to +17 V
−65°C to +150°C
−40°C to +85°C
−40°C to +125°C
JEDEC J-STD-020
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
THERMAL DATA
Absolute maximum ratings apply individually only, not in combination. Exceeding the junction temperature (TJ) limit can
cause damage to the ADP2370/ADP2371. Monitoring ambient
temperature does not guarantee that TJ is within the specified
temperature limits. The maximum ambient temperature may
require derating in applications with high power dissipation and
poor thermal resistance.
In applications with moderate power dissipation and low
printed circuit board (PCB) thermal resistance, the maximum
ambient temperature can exceed the maximum limit as long
as the junction temperature is within specification limits. The
junction temperature of the device is dependent on the ambient
temperature, the power dissipation of the device, and the junction
to ambient thermal resistance of the package (θJA).
Maximum junction temperature (TJ) is calculated from the
ambient temperature (TA) and power dissipation (PD) using
the formula
of θJA can vary, depending on PCB material, layout, and
environmental conditions.
The specified values of θJA are based on a 4-layer, 4 in. × 3 in.
circuit board. See JESD 51-7, High Effective Thermal Conductivity Test Board for Leaded Surface Mount Packages, for detailed
information on board construction. For more information, see
Application Note AN-772, A Design and Manufacturing Guide for
the Lead Frame Chip Scale Package (LFCSP).
ΨJB is the junction to board thermal characterization parameter
with units of °C/W. The ΨJB of the package is based on modeling
and calculation using a 4-layer board. The JESD51-12, Guidelines
for Reporting and Using Electronic Package Thermal Information,
states that thermal characterization parameters are not the same
as thermal resistances. ΨJB measures the component power flowing
through multiple thermal paths rather than a single path as in
thermal resistance, θJB. Therefore, ΨJB thermal paths include
convection from the top of the package as well as radiation
from the package, factors that make ΨJB more useful in realworld applications. Maximum junction temperature (TJ) is
calculated from the board temperature (TB) and power
dissipation (PD) using the formula
TJ = TB + (PD × ΨJB)
For more detailed information regarding ΨJB, see JESD51-12
and JESD51-8, Integrated Circuit Thermal Test Method Environmental Conditions—Junction-to-Board.
THERMAL RESISTANCE
θJA and ΨJB are specified for the worst-case conditions, that is, a
device soldered in a circuit board for surface-mount packages.
θJC is a parameter for surface-mount packages with top mounted
heat sinks.
Table 4. Thermal Resistance
Package Type
8-Lead 3 mm × 3 mm LFCSP
ESD CAUTION
TJ = TA + (PD × θJA)
Junction-to-ambient thermal resistance (θJA) of the package
is based on modeling and calculation using a 4-layer board.
θJA is highly dependent on the application and board layout. In
applications where high maximum power dissipation exists,
close attention to thermal board design is required. The value
Rev. D | Page 6 of 32
θJA
36.7
θJC
23.5
ΨJB
17.2
Unit
°C/W
Data Sheet
ADP2370/ADP2371
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
ADP2370/ADP2371
VIN 1
EN 3
SYNC 4
8 PGND
TOP VIEW
(Not to
Scale)
7 SW
6 PG
5 FB
NOTES
1. THE EXPOSED PAD ON THE BOTTOM OF THE PACKAGE ENHANCES
THE THERMAL PERFORMANCE AND IS ELECTRICALLY CONNECTED
TO GROUND INSIDE THE PACKAGE. THE EXPOSED PAD MUST BE
CONNECTED TO THE GROUND PLANE ON THE CIRCUIT BOARD
FOR PROPER OPERATION.
09531-002
FSEL 2
Figure 2. Pin Configuration
Table 5. Pin Function Descriptions
Pin No.
1
2
3
4
Mnemonic
VIN
FSEL
EN
SYNC
5
6
7
8
FB
PG
SW
PGND
EPAD
Description
Power Input.
Frequency Select. High = 1.2 MHz, low = 600 kHz.
Enable. Enable input with precision thresholds.
Synchronize. This pin is used to synchronize the device to an external 600 kHz to 1.2 MHz clock or forces
PWM mode when it is held high. SYNC held low forces automatic PWM/PSM operation.
Feedback. This pin provides feedback from the output.
Power Good. PG is an open-drain output.
Switch. This pin serves as the connection from the power MOSFETs to the inductor.
Power Ground.
Exposed Pad. The exposed pad on the bottom of the package enhances the thermal performance and is
electrically connected to ground inside the package. The exposed pad must be connected to the ground
plane on the circuit board for proper operation.
Rev. D | Page 7 of 32
ADP2370/ADP2371
Data Sheet
TYPICAL PERFORMANCE CHARACTERISTICS
BUCK OUTPUT
Using recommended inductor values, IOUT = 10 mA, CIN = COUT = 10 µF, automatic PSM/PWM mode, TA = 25°C, unless otherwise noted.
0.65
1.30
25
0.63
1.26
15
10
4
5
1.22
0.59
1.18
1.16
0.57
6
7
8
9
10
11
12
13
14
15
1.12
0.55
1.10
16
3
5
7
9
11
13
15
INPUT VOLTAGE (V)
INPUT VOLTAGE (V)
Figure 3. Quiescent Supply Current vs. Input Voltage, Nonswitching,
Different Temperatures
Figure 6. Switching Frequency vs. Input Voltage, FPWM Mode
800
3.40
+125°C
+85°C
+25°C
–5°C
–40°C
3.35
700
650
600
550
3.30
3.25
3.20
3.15
500
3
4
5
6
7
8
9
10
11
12
13
14
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
3.10
–40
15
–5
INPUT VOLTAGE (V)
25
85
125
TEMPERATURE (°C)
Figure 4. FPWM Quiescent Supply Current vs. Input Voltage, Nonswitching,
Different Temperatures
Figure 7. Output Voltage vs. Temperature, VOUT = 3.3 V, VIN = 7.3 V,
Different Loads
0.65
1.30
09531-007
OUTPUT VOLTAGE (V)
750
09531-004
FPWM QUIESCENT CURRENT (µA)
0.61
1.2MHz
1.20
1.14
0
3
1.24
5.20
1.28
5.15
0.63
1.26
0.61
1.20
1.2MHz
0.59
1.18
1.16
5.05
5.00
4.95
4.90
0.57
1.14
4.85
1.10
–45
–25
–5
15
35
55
75
TEMPERATURE (°C)
95
115
0.55
135
09531-005
1.12
Figure 5. Switching Frequency vs. Temperature, FPWM Mode, VIN = 8 V
Rev. D | Page 8 of 32
4.80
–40
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
–5
25
85
125
TEMPERATURE (°C)
Figure 8. Output Voltage vs. Temperature, VOUT = 5 V, VIN = 7.2 V,
Different Loads
09531-008
600kHz
OUTPUT VOLTAGE (V)
1.22
FREQUENCY (MHz)
FREQUENCY (MHz)
5.10
1.24
09531-006
+125°C
+85°C
+25°C
–5°C
–40°C
5
600kHz
FREQUENCY (MHz)
FREQUENCY (MHz)
20
09531-003
QUIESCENT CURRENT (µA)
1.28
Data Sheet
ADP2370/ADP2371
3.40
1.25
3.35
1.21
1.19
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
1.15
–40
3.25
3.8V
4.55V
6.05V
7.30V
10.55V
12.05V
15.05V
3.20
3.15
–5
25
85
125
TEMPERATURE (°C)
3.10
09531-009
1.17
3.30
0.1
1
10
1.90
5.20
1.85
(–% LIMIT)
(+% LIMIT)
50mA
100mA
300mA
800mA
0.1mA
1mA
5mA
10mA
5.15
5.10
VOUT (V)
5.05
1.80
1.70
–40
4.90
4.85
–5
25
85
125
TEMPERATURE (°C)
4.80
5
7
11
9
13
15
VIN (V)
Figure 10. Output Voltage vs. Temperature, VOUT = 1.8 V, VIN = 7.2 V,
Different Loads
Figure 13. Line Regulation, VOUT = 5.0 V, Different Loads
3.40
5.20
5.15
3.30
3.25
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
3.15
3
5
5.05
5.00
4.95
4.90
4.85
7
9
11
13
15
INPUT VOLTAGE (V)
09531-011
3.20
5.10
4.80
0.1
5.40V
6.00V
7.20V
9.00V
10.80V
12.00V
15.05V
1
10
100
LOAD (mA)
Figure 11. Line Regulation, VOUT = 3.3 V, Different Loads
Figure 14. Load Regulation, VOUT = 5.0 V
Rev. D | Page 9 of 32
1000
09531-014
OUTPUT VOLTAGE (V)
3.35
3.10
09531-113
1.75
5.00
4.95
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
09531-010
OUTPUT VOLTAGE (V)
1000
Figure 12. Load Regulation, VOUT = 3.3 V
Figure 9. Output Voltage vs. Temperature, VOUT = 1.2 V, VIN = 4 V,
Different Loads
OUTPUT VOLTAGE (V)
100
LOAD (mA)
09531-012
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
1.23
ADP2370/ADP2371
Data Sheet
1.25
1.90
1.24
1.22
1.21
1.20
1.19
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
1.17
1.16
1.15
3
1.80
1.75
5
7
9
11
13
15
INPUT VOLTAGE (V)
1.24
90
1.23
80
1.22
70
EFFICIENCY (%)
100
1000
1.21
1.20
3.20V
3.95V
5.45V
7.20V
9.95V
11.95V
15.20V
60
50
3.80V
4.55V
6.05V
7.30V
10.55V
12.05V
15.05V
40
30
20
10
1.16
1
10
100
1000
LOAD (mA)
0
0.01
09531-016
1.15
0.1
0.10
1.0
10
100
1000
LOAD (mA)
09531-019
OUTPUT VOLTAGE (V)
100
1.17
10
Figure 18. Load Regulation, VOUT = 1.8 V
1.25
1.18
1
LOAD (mA)
Figure 15. Line Regulation, VOUT = 1.2 V, Different Loads
1.19
3.20V
3.95V
5.45V
7.20V
9.95V
11.95V
15.20V
1.70
0.1
09531-015
1.18
1.85
09531-018
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
1.23
Figure 19. Efficiency vs. Load Current, VOUT = 3.3 V, Different Input Voltages
Figure 16. Load Regulation, VOUT = 1.2 V
1.90
100
90
EFFICIENCY (%)
70
1.80
0.1mA
1mA
5mA
10mA
50mA
100mA
300mA
800mA
5
50
–40°C
–5°C
+25°C
+85°C
+125°C
40
30
20
10
1.70
3
60
7
9
11
13
15
INPUT VOLTAGE (V)
Figure 17. Line Regulation, VOUT = 1.8 V, Different Loads
0
0.01
0.10
1.0
10
LOAD (mA)
100
1000
09531-020
1.75
09531-017
OUTPUT VOLTAGE (V)
80
1.85
Figure 20. Efficiency vs. Load Current, VOUT = 3.3 V, Different Temperatures,
VIN = 7.3 V
Rev. D | Page 10 of 32
ADP2370/ADP2371
100
100
90
90
80
80
70
70
EFFICIENCY (%)
60
50
5.4V
6.0V
7.2V
9.0V
10.8V
12.8V
15.0V
40
30
20
10
100
1000
90
90
80
80
70
70
EFFICIENCY (%)
100
50
–40°C
–5°C
+25°C
+85°C
+125°C
40
30
20
10
100
1000
LOAD (mA)
Figure 22. Efficiency vs. Load Current, VOUT = 5.0 V, Different Temperatures
0
0.01
90
80
80
70
70
EFFICIENCY (%)
90
50
40
3.20V
3.95V
5.50V
7.20V
9.95V
12.45V
15.20V
10
0
0.01
0.10
1.0
1.0
10
100
1000
60
50
–40°C
–5°C
+25°C
+85°C
+125°C
40
30
20
10
10
LOAD (mA)
100
1000
0
0.01
09531-023
20
0.10
Figure 25. Efficiency vs. Load Current, VOUT = 1.8 V, Different Input Voltages
100
30
3.20V
3.95V
5.50V
7.20V
9.95V
12.45V
15.20V
LOAD (mA)
100
60
1000
40
10
10
100
50
30
1.0
10
60
20
0.10
1.0
Figure 24. Efficiency vs. Load Current, VOUT = 1.2 V, Different Temperatures,
VIN = 4 V
100
60
0.10
LOAD (mA)
09531-022
EFFICIENCY (%)
0
0.01
09531-025
1.0
09531-021
0.10
09531-024
10
Figure 21. Efficiency vs. Load Current, VOUT = 5.0 V, Different Input Voltages
0
0.01
–40°C
–5°C
+25°C
+85°C
+125°C
40
20
LOAD (mA)
EFFICIENCY (%)
50
30
10
0
0.01
60
Figure 23. Efficiency vs. Load Current, VOUT = 1.2 V, Different Input Voltages
0.10
1.0
10
LOAD (mA)
100
1000
09531-026
EFFICIENCY (%)
Data Sheet
Figure 26. Efficiency vs. Load Current, VOUT = 1.8 V, Different Temperatures,
VIN = 4 V
Rev. D | Page 11 of 32
ADP2370/ADP2371
Data Sheet
90
VIN
85
80
600kHz
EFFICIENCY (%)
75
INDUCTOR CURRENT
1.2MHz
70
1
65
60
VOUT
55
2
3
09531-030
50
45
0.1
1
10
100
1000
LOAD (mA)
CH1 500mA Ω BW CH2 20.0mV
CH3 1.00V BW
09531-027
40
0.01
Figure 27. Efficiency vs. Load Current, Different Switching Frequency,
VOUT = 1.8 V, VIN = 9 V
B
M10.0µs A CH3
W
T
4.56V
11.0%
Figure 30. Line Transient, VOUT = 1.2 V, PSM Mode, 100 mA, VIN1 = 4 V to 5 V,
2 μs Rise Time, CIN = 3.3 μF
VIN
VIN
INDUCTOR CURRENT
1
INDUCTOR CURRENT
1
VOUT
VOUT
2
3
2
CH1 500mA Ω BW CH2 20.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
CH1 500mA Ω BW CH2 10.0mV
CH3 1.00V BW
4.56V
11.00%
Figure 28. Line Transient, VOUT = 1.8 V, PSM Mode, 100 mA, VIN1 = 4 V to 5 V,
2 μs Rise Time, CIN = 3.3 μF
B
M10.0µs A CH3
W
T
5.44V
10.80%
Figure 31. Line Transient, VOUT = 1.2 V, PWM Mode, 800 mA, VIN1 = 4 V to 5 V,
2 μs Rise Time, CIN = 3.3 μF
VIN
1
09531-031
09531-028
3
VIN
INDUCTOR CURRENT
INDUCTOR CURRENT
1
VOUT
VOUT
CH1 200mA Ω BW CH2 20.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
3
4.64V
11.20%
Figure 29. Line Transient, VOUT = 1.8 V, PWM Mode, 800 mA, VIN1 = 4 V to 5 V,
2 μs Rise Time, CIN = 3.3 μF
09531-032
09531-029
2
CH1 200mA Ω BW CH2 20.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
6.78V
11.40%
Figure 32. Line Transient, VOUT = 3.3 V, PSM Mode, 100 mA, VIN1 = 6 V to 7 V,
2 μs Rise Time, CIN = 3.3 μF
Rev. D | Page 12 of 32
Data Sheet
ADP2370/ADP2371
LOAD CURRENT
VIN
1
INDUCTOR CURRENT
VOUT
2
VOUT
09531-033
1
CH1 200mA Ω BW CH2 10.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
3
6.78V
11.40%
Figure 33. Line Transient, VOUT = 3.3 V, PWM Mode, 800 mA, VIN1 = 6 V to 7 V,
2 μs Rise Time, CIN = 3.3 μF
09531-036
INDUCTOR CURRENT
2
CH1 500mA Ω BW CH2 50.0mV
CH3 500mA Ω BW
B
W
M20.0µs A CH1
T
560mA
10.40%
Figure 36. Load Transient, VOUT = 1.8 V, 300 mA to 800 mA,
Load Current Rise Time = 200 ns
VIN
LOAD CURRENT
1
INDUCTOR CURRENT
VOUT
1
2
VOUT
2
3
CH1 200mA Ω BW CH2 50.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
3
6.74V
10.60%
Figure 34. Line Transient, VOUT = 5 V, PSM Mode, 100 mA, VIN1 = 6 V to 7 V,
2 μs Rise Time, CIN = 3.3 μF
09531-037
09531-034
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 100mV
CH3 500mA Ω BW
B
W
M40.0µs A CH1
T
320mA
72.00%
Figure 37. Load Transient, VOUT = 1.8 V, 10 mA to 800 mA,
Load Current Rise Time = 200 ns
VIN
LOAD CURRENT
1
VOUT
INDUCTOR CURRENT
2
VOUT
INDUCTOR CURRENT
CH1 200mA Ω BW CH2 10.0mV
CH3 1.00V BW
B
M10.0µs A CH3
W
T
09531-038
1
09531-035
2
3
CH1 100mA Ω BW CH2 20.0mV
CH3 200mA Ω BW
6.52V
11.00%
Figure 35. Line Transient, VOUT = 5 V, PWM Mode, 800 mA, VIN1 = 6 V to 7 V,
2 μs Rise Time, CIN = 3.3 μF
Rev. D | Page 13 of 32
B
W
M10.0µs A CH1
T
76.0mA
50.40%
Figure 38. Load Transient, VOUT = 1.8 V,10 mA to 110 mA,
Load Current Rise Time = 200 ns
ADP2370/ADP2371
Data Sheet
LOAD CURRENT
LOAD CURRENT
1
1
VOUT
VOUT
2
2
3
CH1 200mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
B
W
M20.0µs A CH1
T
3
208mA
50.40%
Figure 39. Load Transient, VOUT = 1.8 V,100 mA to 300 mA,
Load Current Rise Time = 200 ns
CH1 100mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
B
W
M20.0µs A CH1
T
46.0mA
50.40%
Figure 42. Load Transient, VOUT = 3.3 V, 10 mA to 110 mA,
Load Current Rise Time = 200 ns
LOAD CURRENT
LOAD CURRENT
1
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 50.0mV
CH3 500mA Ω BW
B
W
M40.0µs A CH1
T
3
580mA
10.20%
Figure 40. Load Transient, VOUT = 3.3 V, 300 mA to 800 mA,
Load Current Rise Time = 200 ns
09531-043
INDUCTOR CURRENT
09531-040
3
09531-042
INDUCTOR CURRENT
09531-039
INDUCTOR CURRENT
CH1 200mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
B
W
M20.0µs A CH1
T
184mA
29.80%
Figure 43. Load Transient, VOUT = 3.3 V, 100 mA to 300 mA,
Load Current Rise Time = 200 ns
LOAD CURRENT
LOAD CURRENT
1
1
VOUT
VOUT
2
2
09531-041
3
CH1 500mA Ω BW CH2 200mV
CH3 500mA Ω BW
B
W
M40.0µs A CH1
T
3
530mA
71.80%
Figure 41. Load Transient, VOUT = 3.3 V, 10 mA to 800 mA,
Load Current Rise Time = 200 ns
09531-044
INDUCTOR CURRENT
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 50.0mV
CH3 500mA Ω BW
B
W
M10.0µs A CH1
T
560mA
10.40%
Figure 44. Load Transient, VOUT = 1.2 V, 300 mA to 800 mA,
Load Current Rise Time = 200 ns, VIN = 5 V
Rev. D | Page 14 of 32
Data Sheet
ADP2370/ADP2371
LOAD CURRENT
LOAD CURRENT
1
1
VOUT
2
VOUT
2
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 100mV
CH3 500mA Ω BW
B
W
M40.0µs A CH1
T
3
320mA
72.00%
Figure 45. Load Transient, VOUT = 1.2 V, 10 mA to 800 mA, Load Current Rise
Time = 200 ns, VIN = 5 V
09531-048
3
09531-045
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 100mV
CH3 500mA Ω BW
B
W
M20.0µs A CH1
T
530mA
10.00%
Figure 48. Load Transient, VOUT = 5 V, 300 mA to 800 mA, Load Current Rise
Time = 200 ns, VIN = 8 V
LOAD CURRENT
LOAD CURRENT
1
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
CH1 100mA Ω BW CH2 20.0mV
CH3 500mA Ω BW
B
W
M10.0µs A CH1
T
09531-049
3
09531-046
INDUCTOR CURRENT
3
CH1 500mA Ω BW CH2 200mV
CH3 500mA Ω BW
112mA
50.40%
Figure 46. Load Transient, VOUT = 1.2 V,10 mA to 110 mA, Load Current Rise
Time = 200 ns, VIN = 5 V
B
W
M40.0µs A CH1
T
320mA
72.00%
Figure 49. Load Transient, VOUT = 5 V, 1 mA to 800 mA, Load Current Rise
Time = 200 ns, VIN = 8 V
LOAD CURRENT
LOAD CURRENT
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
3
09531-047
INDUCTOR CURRENT
CH1 100mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
B
W
M20.0µs A CH1
T
09531-050
1
3
CH1 100mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
220mA
50.40%
Figure 47. Load Transient, VOUT = 1.2 V,100 mA to 300 mA, Load Current Rise
Time = 200 ns, VIN = 5 V
B
W
M20.0µs A CH1
T
80.0mA
50.40%
Figure 50. Load Transient, VOUT = 5 V,10 mA to 110 mA, Load Current Rise
Time = 200 ns, VIN = 8 V
Rev. D | Page 15 of 32
ADP2370/ADP2371
Data Sheet
VIN
LOAD CURRENT
1
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
INDUCTOR CURRENT
CH1 200mA Ω BW CH2 100mV
CH3 200mA Ω BW
B
W
M20.0µs A CH1
T
09531-054
09531-051
3
3
CH1 5.00V BW
CH2 2.00V BW
CH3 200mA Ω BW
208mA
30.40%
Figure 51. Load Transient, VOUT = 5 V, 100 mA to 300 mA, Load Current Rise
Time = 200 ns, VIN = 8 V
M100µs
T
A CH1
2.50V
10.00%
Figure 54. Startup, VOUT = 3.3 V, 10 mA
VIN
VIN
1
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
INDUCTOR CURRENT
CH1 5.00V BW
CH2 1.00V BW
CH3 200mA Ω BW
M100µs
T
A CH1
09531-055
3
09531-052
3
CH1 5.00V BW
CH2 2.00V BW
CH3 500mA Ω BW
2.50V
10.00%
Figure 52. Startup, VOUT = 1.8 V, 10 mA
M100µs
T
A CH1
2.50V
10.00%
Figure 55. Startup, VOUT = 3.3 V, 800 mA
VIN
VIN
1
1
VOUT
VOUT
2
2
INDUCTOR CURRENT
INDUCTOR CURRENT
CH1 5.00V BW
CH2 1.00V BW
CH3 500mA Ω BW
M100µs
T
A CH1
09531-056
3
09531-053
3
CH1 5.00V BW
CH2 1.00V BW
CH3 200mA Ω BW
2.50V
10.00%
Figure 53. Startup, VOUT = 1.8 V, 800 mA
M100µs
T
A CH1
10.00%
Figure 56. Startup, VOUT = 1.2 V, 10 mA, VIN = 5 V
Rev. D | Page 16 of 32
2.50V
Data Sheet
ADP2370/ADP2371
250
1
VOUT
2
INDUCTOR CURRENT
09531-057
3
CH1 5.00V BW
CH2 500mV BW
CH3 500mA Ω BW
M100µs
T
A CH1
200
150
100
–40°C
–5°C
+25°C
+85°C
+125°C
50
0
2.50V
3
5
7
9
11
13
15
INPUT VOLTAGE (V)
10.00%
Figure 57. Startup, VOUT = 1.2 V, 800 mA, VIN = 5 V
09531-060
PSM TO PWM THRESHOLD (mA)
VIN
Figure 60. PSM to PWM Mode Transition vs. Input Voltage,
Different Temperatures
1200
VIN
1150
1
OC THRESHOLD (mA)
1100
2
INDUCTOR CURRENT
1050
1000
5.4V
7.2V
12.0V
15.0V
950
900
09531-058
3
CH1 5.00V BW
CH2 2.00mV BW
CH3 200mA Ω BW
M100µs
T
A CH1
850
800
–60
2.50V
–40
–20
0
20
40
60
80
100
120
140
TEMPERATURE (°C)
10.00%
09531-061
VOUT
Figure 61. Overcurrent Limit vs. Temperature, VOUT = 5 V,
Different Input Voltages
Figure 58. Startup, VOUT = 5 V, 10 mA, VIN = 7 V
0.05
VIN
0.04
RIPPLE VOLTAGE (V p-p)
1
VOUT
2
INDUCTOR CURRENT
0.03
3.2V
5.0V
9.0V
15V
0.02
0.01
CH1 5.00V BW
CH2 2.00mV BW
CH3 500mA Ω BW
M100µs
T
A CH1
0
2.50V
10.00%
Figure 59. Startup, VOUT = 5 V, 800 mA, VIN = 7 V
0
100
200
300
400
500
LOAD CURRENT (mA)
600
700
800
09531-062
09531-059
3
Figure 62. Output Ripple vs. Load Current, VOUT = 1.2 V, Different Input
Voltages, Automatic Mode
Rev. D | Page 17 of 32
Data Sheet
0.05
0.025
0.04
0.020
RIPPLE VOLTAGE (V p-p)
0.03
3.2V
5.0V
9.0V
15V
0.02
0.015
4V
5V
9V
15V
0.010
0.005
0.01
0
100
200
300
400
500
600
700
800
LOAD CURRENT (mA)
0
09531-063
0
Figure 63. Output Ripple vs. Load Current, VOUT = 1.8 V, Different Input
Voltages, Automatic Mode
0
200
300
400
500
600
700
800
LOAD CURRENT (mA)
Figure 66. Output Ripple vs. Load Current, VOUT = 3.3 V, Different Input
Voltages, Force PWM Mode
1.0
0.08
0.9
0.8
0.06
0.7
0.04
RDSON (Ω)
RIPPLE VOLTAGE (V p-p)
100
09531-066
RIPPLE VOLTAGE (V p-p)
ADP2370/ADP2371
4.5V
5.0V
9.0V
15V
3.0V
3.5V
4.0V
5.0V
6.0V
7.0V
10.0V
0.6
0.5
0.4
0.3
0.02
0.2
0
100
200
300
400
500
600
700
800
LOAD CURRENT (mA)
0
–40
09531-064
0
Figure 64. Output Ripple vs. Load Current, VOUT = 3.3 V, Different Input
Voltages, Automatic Mode
0
20
40
60
80
100
120
TEMPERATURE (°C)
Figure 67. PMOS RDSON vs. Temperature at 400 mA, Different Input Voltages
1.0
0.10
0.9
0.8
0.08
0.7
RDSON (Ω)
RIPPLE VOLTAGE (V p-p)
–20
09531-067
0.1
0.06
5.8V
6.0V
9.0V
15V
0.04
3.0V
3.5V
4.0V
5.0V
6.0V
7.0V
10.0V
0.6
0.5
0.4
0.3
0.2
0.02
0
100
200
300
400
500
LOAD CURRENT (mA)
600
700
800
0
–40
09531-065
0
Figure 65. Output Ripple vs. Load Current, VOUT = 5 V, Different Input
Voltages, Automatic Mode
–20
0
20
40
60
TEMPERATURE (°C)
80
100
120
09531-068
0.1
Figure 68. NMOS RDSON vs. Temperature at 400 mA, Different Input Voltages
Rev. D | Page 18 of 32
Data Sheet
ADP2370/ADP2371
1.0
1.0
+125°C
+85°C
+25°C
–5°C
–40°C
0.9
0.8
0.7
0.6
0.6
RDSON (Ω)
0.7
0.5
0.4
0.4
0.3
0.2
0.2
0.1
0.1
0
3
4
5
6
7
INPUT VOLTAGE (V)
8
9
10
+125°C
+85°C
+25°C
–5°C
–40°C
0.5
0.3
0
09531-069
RDSON (Ω)
0.8
3
4
5
6
7
INPUT VOLTAGE (V)
Figure 69. PMOS RDSON vs. Input Voltage at 400 mA, Different Temperatures
8
9
10
09531-070
0.9
Figure 70. NMOS RDSON vs. Input Voltage at 400 mA, Different Temperatures
Rev. D | Page 19 of 32
ADP2370/ADP2371
Data Sheet
THEORY OF OPERATION
5V
VIN
REG
1.2V
VSW
EN_PREC
EN
VIN
STANDBY
1.0V
P_ILIMIT
1.2A
VIN
VIN
UVLO
2.95V
RDSON × Kr
IMIN
N_ILIMIT
200mA
Kr
–0.5A – (PWM)
VIN
SW
0A – (PSM)
RDSON × Kr
PWM
VIN
CONTROL
LOGIC
ADP2371
ONLY
SLOPE COMP ISLOPE
PGND
PSM
0.808V
0.8V
SYNC
H = FPWM
L = PWM/PSM
FSEL
H = 1.2MHz
L = 600kHz
OSCILLATOR
DEFAULT = 1.2MHz
VOUT ÷ 2 FREQUENCY
FOLDBACK
FB
150°C
135°C
THSD
ICOMP
PG
VTOL
VCOMP
gM
0.8V
0.736V
0.696V
FB
09531-071
SOFT
START
Figure 71. Functional Block Diagram
The ADP2370/ADP2371 use a high speed, current mode, constant
frequency PWM control scheme for excellent stability and transient response. To ensure the longest battery life in portable
applications, the ADP2370/ADP2371 has a power saving mode.
Under light load conditions, the output capacitor is charged as
needed to maintain regulation; otherwise, the ADP2370/ADP2371
enter sleep mode, a low 14 μA quiescent state. The architecture
ensures smooth transitions from PWM mode to and from PSM,
and maintains high efficiencies at light loads. The following sections describe the two modes of operation and provide detailed
descriptions of the ADP2370/ADP2371 features.
PWM OPERATION
The ADP2370/ADP2371 PWM mode is a fixed frequency,
1.2 MHz typical, current mode architecture. Use the SYNC pin
to synchronize the regulator to an external clock frequency or
use the FSEL pin to select an internal clock frequency of
600 kHz or 1.2 MHz.
The ADP2370/ADP2371 use a constant slope compensation
scheme where the inductor scales with the output voltage. The
equation for choosing the inductor for a particular output
voltage is
L=
1.2 × VOUT
0.478 × f SW
See the Applications Information section for details regarding
choosing an appropriate inductor value.
Cycle to cycle operation of the PWM mode begins with the
falling edge of the internal clock. Note that when using an
external clock, the rising edge synchronizes the regulator and
the falling edge is determined by the internal clock, typically a
25 ns pulse width. The falling edge of the clock starts the cycle
by turning on the high-side switch, which produces a positive
di/dt current in the inductor. The PWM comparator controls
when the high-side switch turns off. The positive input of the
comparator monitors the peak inductor current via the SW node.
Rev. D | Page 20 of 32
Data Sheet
ADP2370/ADP2371
The negative side of the comparator input voltage is set by the
voltage control loop minus the slope compensation. When the
high-side switch turns off, the low-side switch turns on for the
remainder of the clock period.
Figure 72 and Figure 73 illustrate how the output voltage and
inductor current change with loads and transitions in and out of
PSM operation. The output voltage ripple in PSM is ~40 mV p-p,
and the ripple in PWM is <10 mV p-p.
While in PWM/PSM mode, the low-side switch turns off when
the inductor current reaches zero, operating in discontinuous
conduction (DCC) mode. If SYNC is tied high to force the device
into PWM only mode, the low-side switch stays on until the
next clock cycle or until the inductor current reaches the
negative current limit.
LOAD CURRENT
1
VOUT
2
PSM OPERATION
As long as the required peak inductor current is above IMIN, the
regulator remains in PWM mode. As the load decreases, the
PSM circuitry prevents the peak inductor current from dropping
below the PSM peak current value. This circuitry causes the
regulator to supply more current to the output filter than the
load requires, resulting in the output voltage increasing and the
output of the internal compensation node of the error amplifier,
VCOMP, decreasing.
When the FB pin voltage rises above 1% of the nominal output
voltage and the VCOMP node voltage is below a predetermined
PSM threshold voltage level, the regulator enters sleep mode.
While in sleep mode, the high-side and low-side switches and a
majority of the circuitry are disabled to allow for a low sleep
mode quiescent current as well as high efficiency performance.
During sleep mode, the output voltage decreases as the output
capacitor discharges into the load. Fixed frequency operation
starts when the FB voltage reaches the nominal output voltage.
When the load requirement increases past the IMIN peak current
level, the VCOMP node rises and the PWM control loop sets the
duty cycle. While the part is entering and exiting sleep mode,
the PSM voltage ripple is larger than 1% because of the delay in
the comparators.
Rev. D | Page 21 of 32
INDUCTOR CURRENT
09531-072
3
CH1 200mA Ω
CH3 200mA Ω
B
B
W
CH2 50.0mV
B
W
W
M20.00µs A CH1
T
156mA
50.40%
Figure 72. PSM to PWM Transition Waveforms, VOUT = 1.8 V,
10 mA Load to 300 mA Load
LOAD CURRENT
1
VOUT
2
INDUCTOR CURRENT
09531-073
The ADP2370/ADP2371 smoothly transition to the variable
frequency PSM operation. The ADP2370/ADP2371 select a
minimum current value, IMIN, for the peak current of the inductor
based on the input and output voltages. The design of the IMIN
value is based on the recommended inductor values. Deviating
from the recommended inductor value for a particular output
voltage results in shifting the PSM to PWM threshold and could
result in the device entering DCC mode.
3
CH1 200mA Ω BW CH2 50.0mV
CH3 200mA Ω BW
B
W
M20.00µs A CH1
T
156mA
50.40%
Figure 73. PWM to PSM Transition Waveforms, VOUT = 1.8 V,
300 mA Load to 10 mA Load
ADP2370/ADP2371
Data Sheet
FEATURES DESCRIPTIONS
PRECISION ENABLE
UNDERVOLTAGE LOCKOUT
The enable circuit of the ADP2370/ADP2371 minimizes the
input current during shutdown and simultaneously provides
an accurate enable threshold. When the enable input voltage
is below 400 mV, the regulators are in shutdown mode and the
supply current is typically 1.2 μA. As the enable input voltage
rises above the standby enable threshold of 1.0 V, the internal
bias currents and voltages are activated, turning on the precision
enable circuitry. This allows the precision enable circuitry to
detect accurately when the EN pin voltage exceeds the precision
enable rising threshold of 1.2 V.
To protect against battery discharge, an undervoltage lockout
(UVLO) circuit is incorporated into the ADP2370/ADP2371.
When the input voltage drops below the UVLO threshold, the
ADP2370/ADP2371 shuts down, and both the power switch and
synchronous rectifier turn off. Once the input voltage rises
above the UVLO threshold, the soft start period is initiated and
the device is enabled.
FORCED PWM OR PWM/PSM SELECTION
Connecting the SYNC pin to a voltage greater than 1.2 V forces
the device to operate permanently in the PWM mode. This means
that the ADP2370/ADP2371 continue to operate at a fixed frequency even when the output current is less than the PWM/PSM
threshold. In PWM mode, the efficiency is lower compared to the
PSM mode during light loads. The low-side NMOS remains on
when the output current drops to less than zero thereby preventing
the device from entering discontinuous conduction (DCC) mode.
It is possible to switch from FPWM mode to the power-save
mode during operation by pulling the SYNC pin low. The
flexible configuration of the SYNC pin during operation of
the device allows for efficient power management.
Connecting the SYNC pin to a voltage less than 0.4 V allows
the part to operate in either PWM or PSM modes, depending on
the output current. Whenever the average output current goes
below the PWM/PSM threshold, the ADP2370/ADP2371 enter
PSM mode operation. During PSM mode the part operates with
reduced switching frequency and with a minimal quiescent current to maintain high efficiency. The low-side NMOS turns off
when the output current reaches zero, causing the part to operate
in DCC mode.
QUICK OUTPUT DISCHARGE (QOD) FUNCTION
The ADP2371 includes an output discharge resistor that forces the
output voltage to zero when the buck is disabled. This ensures
that the output of the buck is always in a well-defined state, whether
or not it is enabled. The ADP2370 does not include this output
discharge function.
SHORT-CIRCUIT PROTECTION
The ADP2370/ADP2371 include frequency foldback to prevent
output current runaway on a hard short. When the voltage at
the feedback pin falls below 0.3 V, indicating the possibility of
a hard short at the output, the switching frequency is reduced
to 1/4 of the internal oscillator frequency. The reduction in the
switching frequency gives more time for the inductor to discharge, preventing a runaway of output current.
THERMAL PROTECTION
In the event that the junction temperature on either the ADP2370
or ADP2371 rises above 150°C, the thermal shutdown protection circuit turns off the regulator. Extreme junction temperature
can be the result of high current operation, poor circuit board
design, and/or high ambient temperature. A 20°C hysteresis is
included in the protection circuit so that when a thermal shutdown occurs, the device does not return to operation until the
on-chip temperature drops below 130°C. When exiting a
thermal shutdown, soft start is initiated.
SOFT START
The ADP2370/ADP2371 have an internal soft start function that
ramps the output voltage in a controlled manner upon startup,
thereby limiting the inrush current. This prevents possible input
voltage drops when a battery or a high impedance power source
is connected to the input of the converter. Typical soft start time
is 350 μs. The ADP2370/ADP2371 are also capable of starting up
into a precharged output capacitor. If soft start is invoked when
the output capacitor charge is greater than zero, the device delays
the start of switching until the internal soft start ramp reaches the
corresponding FB voltage. This feature prevents discharging the
output capacitor at the beginning of soft start.
CURRENT LIMIT
The ADP2370/ADP2371 have protection circuitry that limits the
direction and amount of current to 1200 mA that flows through
the power switch and synchronous rectifier, cycle by cycle. The
positive current limit on the power switch limits the amount of
current that can flow from the input to the output. The negative
current limit on the synchronous rectifier prevents the inductor
current from reversing direction and flowing out of the load.
A negative current limit is provided by the ADP2370/ADP2371
to prevent an excessive reverse inductor current when the switching
section sinks current from the load in forced continuous conduction mode. Under negative current-limit conditions, both
the high-side and low-side switches are disabled.
Rev. D | Page 22 of 32
Data Sheet
ADP2370/ADP2371
100% DUTY CYCLE
The ADP2370/ADP2371 enter and exit 100% duty cycle smoothly.
The control loop seeks the next clock cycle while the high-side
switch is engaged. When this occurs, the clock signal is masked
and the PMOS remains on. When the input voltage increases, the
internal VCOMP node decreases its signal to the control loop; thus,
the device stops skipping clock cycles and exits 100% duty cycle.
If the device is synchronized to an external clock, the PSM
mode is disabled and the device stays in forced PWM mode.
Connect FSEL to ground when synchronizing to a frequency
range from 400 kHz to 800 kHz, and connect FSEL to the input
voltage when the external frequency is in the range of 800 kHz
to 1600 kHz. FSEL has an internal pull-down resistor and
defaults to the 600 kHz mode when FSEL is unconnected.
INTERNAL 1.2MHZ
VIN
1
2
3
4
INTERNAL 600kHZ
1
VOUT
SYNC
2
PWM CLOCK (IF FSEL = 1)
INDUCTOR CURRENT
3
B
W
CH1 1.00V
CH2 1.00V BW
CH3 50.0mA Ω BW
M2.00ms
T
A CH1
09531-076
09531-074
PWM CLOCK (IF FSEL = 0)
PWM CLOCK FOLLOWS SYNC UNTIL IT MISSES
4 × 1.2MHZ INTERNAL CLOCK CYCLES
4.90V
Figure 76. Typical SYNC Timing
32.20%
Figure 74. Transition into and out of Dropout in PSM Mode,
VOUT = 5 V, 100 mA Load
SW
1
VIN
VOUT
VOUT
2
INDUCTOR CURRENT
3
4
09531-075
1
3
2
M2.00ms
T
A CH1
CH1 5.00V BW
CH2 100mV
CH3 200mA Ω BW CH4 5.00V
4.90V
B
B
W
M20.0µs
W
T
A CH4
2.00V
20.0%
Figure 77. Typical SYNC Transient, 1.2 MHz to 800 kHz to 1.2 MHz
32.20%
Figure 75. Transition into and out of Dropout in PWM Mode,
VOUT = 5 V, 100 mA Load
SW
SYNCHRONIZING
1
It is possible to synchronize the ADP2370/ADP2371 to an external
clock within a frequency range from 400 kHz to 1.6 MHz. The
device automatically detects the rising edge of the first clock
and synchronizes to the external clock. When the clock signal
stops, the device automatically switches back to the internal
clock and continues operating.
The switchover is initiated when no rising edge on the SYNC
pin can be detected on the internal clock for a duration of four
clock cycles. Therefore, the maximum delay time can be 6.7 μs if
the internal clock is running at its minimum frequency of 600 kHz.
During this time, there is no clock signal available. The output
stops switching until the ADP2370 circuitry switches to the
internal clock signal.
Rev. D | Page 23 of 32
VOUT
2
INDUCTOR CURRENT
3
SYNC
09531-078
CH1 1.00V BW
CH2 1.00V BW
CH3 50.0mA Ω BW
09531-077
SYNC
INDUCTOR CURRENT
4
CH1 5.00V BW
CH2 50.0mV BW M20.0µs A CH4
B
CH3 200mA Ω BW CH4 5.00V
W
T 20.0%
Figure 78. SYNC Transient 1.2 MHz to 800 kHz
2.00V
ADP2370/ADP2371
Data Sheet
SW
1
2
VOUT
INDUCTOR CURRENT
VOUT
ENABLE
3
SYNC
CH1 5.00V BW
CH2 50.0mV BW M2.00µs A CH2
B
CH3 200mA Ω BW CH4 5.00V
W
T 20.0%
–57.0mV
09531-080
09531-079
4
PG
3
2
1
CH1 500mV BW
CH3 5.00V BW
Figure 79. SYNC Transient 800 kHz to 1.2 MHz
CH2 1.00V BW
M40.0µs
T
A CH3
3.40V
10.00%
Figure 80. Typical PG Timing at Startup
POWER GOOD
VOUT
The ADP2370/ADP2371 power-good (PG) output indicates the
state of the monitored output voltage. The PG function is an active
high, open-drain output, requiring an external pull-up resistor that
is typically supplied from the I/O supply rail, as shown in Figure 1.
PG
When the sensed output voltage is below 87% of its nominal value,
the PG pin is held low. When the sensed output voltage rises above
92% of the nominal level, the PG line is pulled high after tRESET.
The PG pin remains high when the sensed output voltage is
above 92% of the nominal output voltage level.
2
09531-081
The typical PG delay when the buck is in PWM mode is 20 μs.
Figure 80 shows the typical PG operation during startup. Figure 81
shows the PG operation when there is a large load transient that
causes the output voltage to fall just below the PG threshold.
LOAD CURRENT
3
1
CH1 500mV BW
CH3 500mAΩ BW
CH2 1.00V BW
M1.00µs A CH3
T
740mA
10.00%
Figure 81. Typical PG Timing with 200 mA to 1100 mA Load Transient
When not using the PG function, remove the pull-up resistor
and leave the PG pin either open or shorted to ground.
Rev. D | Page 24 of 32
Data Sheet
ADP2370/ADP2371
APPLICATIONS INFORMATION
ADIsimPower DESIGN TOOL
OUTPUT CAPACITOR
ADP2370/ADP2371 are supported by the ADIsimPower™ design
tool set. ADIsimPower is a collection of tools that produce
complete power designs optimized for a specific design goal.
The tools enable the user to generate a full schematic, bill of
materials, and calculate performance in minutes. ADIsimPower
can optimize designs for cost, area, efficiency, and parts count
taking into consideration the operating conditions and limitations of the IC and all real external components. For more
information about, and to obtain ADIsimPower design tools,
visit www.analog.com/ADIsimPower. Users can also request
an unpopulated board through the ADIsimPower tool.
Output capacitance is required to minimize the voltage overshoot,
voltage undershoot, and the ripple voltage present on the output.
Capacitors with low equivalent series resistance (ESR) values
produce the lowest output ripple; therefore, use capacitors such as
the X5R dielectric. Do not use Y5V and Z5U capacitors. Y5V
and Z5U capacitors are unsuitable choices because of their large
capacitance variation over temperature and their dc bias voltage
changes. Because ESR is important, select the capacitor using
the following equation:
EXTERNAL COMPONENT SELECTION
where:
ESRCOUT is the ESR of the chosen capacitor.
VRIPPLE is the peak-to-peak output voltage ripple.
Table 6 and Table 7 list external component selections for the
ADP2370/ADP2371 application circuit shown in Figure 82. The
selection of components is dependent on the input voltage, output
voltage, and load current requirements. Additionally, trade-offs
among performance parameters, such as efficiency and transient
response, are made by varying the choice of external components.
ESRCOUT ≤
Use the following equations to determine the output
capacitance:
COUT ≥
VIN
(2π × f SW ) × 2 × L × VRIPPLE
COUT ≥
∆I L
8 × f SW × VRIPPLE
SELECTING THE INDUCTOR
The high frequency switching of the ADP2370/ADP2371 allows
for the use of small surface-mount power inductors. The inductor
value affects the transition from PWM to PSM, efficiency, output
ripple, and current-limit values. Use the following equation to calculate the ideal inductance, which is derived from the inductor
current slope compensation, for a given output voltage and
switching frequency:
L=
1.2 × VOUT
0.478 × f SW
VOUT  VOUT
× 1 −
f SW × L 
VIN
Increasing the output capacitor value has no effect on stability
and may reduce output ripple and enhance load transient response.
When choosing the output capacitor value, it is important to
account for the loss of capacitance due to output voltage dc bias.
INPUT CAPACITOR
An input capacitor is required to reduce input voltage ripple, input
ripple current, and source impedance. Place the input capacitor
as close as possible to the VIN pin. A low ESR X7R- or X5R-type
capacitor is highly recommended to minimize the input voltage
ripple. Use the following equation to determine the rms input
current:
The ripple current is calculated as follows:
∆I L =




where:
fSW is the switching frequency in MHz (1.2 MHz typical).
L is the inductor value in μH.
The dc resistance (DCR) value of the selected inductor affects
efficiency; however, a decrease in this value typically means an
increase in root mean square (rms) losses in the core and skin.
A minimum requirement of the dc current rating of the inductor
is for it to be equal to the maximum load current plus half of
the inductor current ripple, as shown by the following equation:
I PK = I LOAD( MAX ) + (
∆I L
)
2
VRIPPLE
ΔI L
I CIN ≥ I LOAD( MAX )
VOUT (VIN − VOUT )
VIN
I rms ≥ I LOAD( MAX )
VOUT (VIN − VOUT )
VIN
ADJUSTABLE OUTPUT VOLTAGE PROGRAMMING
The ADP2370/ADP2371 feature an adjustable output voltage range
from 0.8 V to 12 V. The output voltage is set by the ratio of two
external resistors, R2 and R3, as shown in Figure 83. The device
servos the output to maintain the voltage at the FB pin at 0.8 V,
referenced to ground; the current in R2 is then equal to 0.8 V/R3
plus the FB pin bias current. The bias current of the FB pin,
10 nA at 25°C, flows through R2 into the FB pin.
The output voltage is calculated using the equation
VOUT = 0.8 V(1 + R2/R3) + (FBI-BIAS)(R2)
Rev. D | Page 25 of 32
ADP2370/ADP2371
Data Sheet
To minimize errors in the output voltage caused by the bias
current of the FB pin, maintain a value of R2 that is less than
250 kΩ. For example, when R2 and R3 each equal 250 kΩ, the
output voltage is 1.6 V. The output voltage error introduced by
the FB pin bias current is 2.5 mV, or 0.156%, assuming a typical
FB pin bias current of 10 nA at 25°C.
Switching Losses
Note that in shutdown mode, the output is turned off and the
divider current is zero.
Estimate switching losses using the following equation:
Select the output inductor and capacitor as described in the
Selecting the Inductor, Output Capacitor, and Input Capacitor
sections, as well as Table 6 for more information.
EFFICIENCY
Efficiency is defined as the ratio of output power to input power.
The high efficiency of the ADP2370/ADP2371 has two distinct
advantages. First, only a small amount of power is lost in the
dc-to-dc converter package, which in turn, reduces thermal
constraints. Second, high efficiency delivers the maximum
output power for the given input power, thereby extending
battery life in portable applications.
Power Switch Conduction Losses
Power switch dc conduction losses are caused by the flow of
output current through the P-channel power switch and the
N-channel synchronous rectifier, which have internal resistances (RDS(ON)) associated with them. The amount of power
loss is approximated by
PSW = (CGATE_P + CGATE_N) × VIN2 × fSW
where:
CGATE_P is the gate capacitance of the internal high-side switch.
CGATE_N is the gate capacitance of the internal low-side switch.
fSW is the switching frequency.
The typical value for gate capacitances, CGATE_P and CGATE_N,
is 150 pF.
Transition Losses
Transition losses occur because the P-channel switch cannot
turn on or turn off instantaneously. In the middle of an SW
node transition, the power switch provides all of the inductor
current. The source-to-drain voltage of the power switch is half
the input voltage, resulting in power loss. Transition losses
increase with both load current and input voltage and occur
twice for each switching cycle.
Use the following equation to estimate transition losses:
PTRAN = VIN/2 × IOUT × (tR + tF) × fSW
where:
tR is the rise time of the SW node.
tF is the fall time of the SW node.
PSW _ COND = (RDS(ON ) _ P × D + RDS(ON ) _ N × (1 − D)) × I OUT 2
where:
D=
Switching losses are associated with the current drawn by the
driver to turn-on and turn-off the power devices at the switching
frequency. Each time a power device gate is turned on and turned
off, the driver transfers a charge from the input supply to the
gate, and then from the gate to ground.
VOUT
VIN
The typical value for the rise and fall times, tR and tF, is 2 ns.
The internal resistance of the power switches increases with temperature and increases when the input voltage is less than 5.5 V.
Inductor Losses
Inductor conduction losses are caused by the flow of current
through the inductor, which has an internal resistance (DCR)
associated with it. Larger size inductors have smaller DCR,
which can decrease inductor conduction losses. Inductor core
losses relate to the magnetic permeability of the core material.
Because the ADP2370/ADP2371 are high switching frequency
dc-to-dc regulators, shielded ferrite core material is recommended
because of its low core losses and low EMI.
To estimate the total amount of power lost in the inductor, use
the following equation:
RECOMMENDED BUCK EXTERNAL COMPONENTS
The recommended external components for use with the
ADP2370/ADP2371 are listed in Table 6 (inductors) and Table 7
(capacitors).
VIN = 6V
CIN
10µF
POWER GOOD
VIN
FSEL
ON
PL = DCR × IOUT + Core Losses
1
8
2
7
3
6
EN
OFF
2
ADP2370/
ADP2371
PGND
SW
PG
6.8µH
VOUT = 3.3V
COUT
10µF
AGND
(EXPOSED PAD)
4
5
FB
09531-082
SYNC
Figure 82. Typical Application, 1.2 MHz, Fixed Output
Rev. D | Page 26 of 32
Data Sheet
ADP2370/ADP2371
VIN = 6V
CIN
10µF
R1
10kΩ
1
8
2
7
FSEL
ON
EN 3
OFF
SYNC
6
POWER GOOD
PGND
SW
PG
6.8µH
VOUT = 1.8V
COUT
10µF
R2
249kΩ
AGND
(EXPOSED PAD)
4
5
FB
R3
200kΩ
09531-083
VIN
ADP2370/
ADP2371
Figure 83. Typical Application, 600 kHz, Adjustable Output
Table 6. Inductors
Vendor
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Coilcraft
Model
XFL4020-222ME
XFL4020-332ME
XFL4020-332ME
XFL4020-472ME
XAL4030-682ME
XAL4030-682ME
XAL4040-103ME
LPS6235-183ML
XFL4020-472ME
XAL4030-682ME
XAL4030-682ME
XAL4040-103ME
XAL4040-103ME
XAL4040-153ME
LPS6235-223ML
LPS6235-333ML
Frequency
1.2 MHz
1.2 MHz
1.2 MHz
1.2 MHz
1.2 MHz
1.2 MHz
1.2 MHz
1.2 MHz
600 kHz
600 kHz
600 kHz
600 kHz
600 kHz
600 kHz
600 kHz
600 kHz
Output
Voltage
1.2
1.5
1.8
2.5
3.0
3.3
5
9
1.2
1.5
1.8
2.5
3.0
3.3
5
9
Ideal Value
(μH)
2.5
3.1
3.8
5.2
6.3
6.9
10.5
18.8
5.0
6.3
7.5
10.5
12.6
13.8
20.9
37.7
Standard Value
(μH)
2.2
3.3
3.3
4.7
6.8
6.8
10
18
4.7
6.8
6.8
10
10
15
22
33
Dimensions
(mm)
4×4×2
4×4×2
4×4×2
4×4×2
4×4×3
4×4×3
4×4×4
6 × 6 × 3.5
4×4×2
4×4×3
4×4×3
4×4×4
4×4×4
4×4×4
6 × 6 × 3.5
6 × 6 × 3.5
ISAT
(A)
4.1
3.1
3.1
2.0
1.9
1.9
1.5
1.7
2.0
1.9
1.9
1.5
1.5
1.3
1.6
1.3
DCR
(mΩ)
24
38
38
57
74
74
92
14
57
74
74
92
92
120
145
130
Table 7. 10 μF Capacitors
Vendor
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Model
GRM32ER7YA106KA12
GRM32DR61E106KA12
GRM31CR61C106KA88
GRM32ER7YA106KA12
GRM32DR61E106KA12
GRM31CR61C106KA88
GRM21BR61C106KE15
Case Size
1210
1210
1206
1210
1210
1206
0805
Voltage Rating
35
25
16
35
25
16
16
Location
Input or Output
Input or Output
Input or Output
Input or Output
Input or Output
Input or Output
Output
Rev. D | Page 27 of 32
Input Voltage
<15 V
<12 V
<8 V
Output
Voltage
<12 V
<9 V
<7 V
<2.5 V
ADP2370/ADP2371
Data Sheet
CAPACITOR SELECTION
Output Capacitor
The ADP2370/ADP2371 are designed for operation with small,
space-saving ceramic capacitors, but function with most commonly
used capacitors provided that the effective series resistance (ESR)
value is carefully considered. The ESR of the output capacitor
affects stability of the control loop. A minimum output capacitance of 7 μF with an ESR of 10 mΩ or less is recommended to
ensure stability of the ADP2370/ADP2371.
Figure 85 depicts the capacitance vs. voltage bias characteristic
of a several 10 μF capacitors in different case sizes and voltage
ratings. The voltage stability of a capacitor is strongly influenced
by the capacitor size and voltage rating. In general, a capacitor in a
larger package or higher voltage rating exhibits better stability.
The temperature variation of the X5R dielectric is about ±15%
over the −40°C to +85°C temperature range and is not a
function of package or voltage rating.
12
11
Transient response to changes in load current is also affected by
output capacitance. Using a larger value of output capacitance
improves the transient response of the ADP2370/ADP2371 to
large changes in load current. Figure 84 shows the transient
response for an output capacitance value of 10 μF.
10µF/25V/1210
10µF/35V/1210
10µF/16V/0805
10µF/16V/1206
10
CAPACITANCE (µF)
9
LOAD CURRENT
8
7
6
5
4
3
1
2
0
0
2
5
10
15
20
25
30
35
DC BIAS VOLTAGE (V)
09531-085
1
VOUT
Figure 85. Capacitance vs. Voltage Characteristic Different Case Sizes
Use Equation 1 to determine the worst-case capacitance,
accounting for capacitor variation over temperature,
component tolerance, and voltage.
3
09531-084
INDUCTOR CURRENT
CH1 500mA Ω BW CH2 50.0mV
CH3 500mA Ω BW
B
W M20.0µs A CH1
T
CEFF = CBIAS × (1 − TEMPCO) × (1 − TOL)
560mA
(1)
where:
CBIAS is the effective capacitance at the operating voltage.
TEMPCO is the worst-case capacitor temperature coefficient.
TOL is the worst-case component tolerance.
10.40%
Figure 84. Output Transient Response, VOUT2 = 1.8 V, COUT = 10 μF,
300 mA to 800 mA, Load Current Rise Time = 200 ns
Input Bypass Capacitor
Connecting a 10 μF capacitor from VIN to GND reduces the
circuit sensitivity to the PCB layout, especially when long input
traces or high source impedance are encountered. If greater than
10 μF of output capacitance is required, increase the input
capacitor to match it to improve the transient response.
In this example, the worst-case TEMPCO over −40°C to +85°C
is assumed to be 15% for an X5R dielectric. The tolerance of the
capacitor (TOL) is assumed to be 10%, and CBIAS is 8.53 μF at 12 V
for the 10 μF, 35 V capacitor in a 1210 package (see Figure 85).
Substituting these values in Equation 1 yields
Input and Output Capacitor Properties
CEFF = 8.53 μF × (1 − 0.15) × (1 − 0.1) = 6.53 μF
Use any good quality ceramic capacitors with the ADP2370/
ADP2371; however they must meet the minimum capacitance
and maximum ESR requirements. Ceramic capacitors are manufactured with a variety of dielectrics, each with different behavior
over temperature and applied voltage. Capacitors must have a
dielectric adequate to ensure the minimum capacitance over the
necessary temperature range and dc bias conditions. X5R or X7R
dielectric capacitors with a voltage rating of 6.3 V to 25 V are
recommended for best performance. Y5V and Z5U dielectrics
are not recommended because of their poor temperature and dc
bias characteristics.
Therefore, the capacitor chosen in this example meets the
minimum capacitance requirement of the ADP2370/ADP2371
over temperature and tolerance at the chosen output voltage.
To guarantee the performance of the ADP2370/ADP2371, it is
imperative that the effects of dc bias, temperature, and
tolerances of the capacitors are evaluated for each application.
Rev. D | Page 28 of 32
Data Sheet
ADP2370/ADP2371
THERMAL CONSIDERATIONS
Table 8. Typical θJA Values
115
105
95
85
75
6400mm2
500mm2
100mm2
TJ MAX
65
55
45
35
25
0
0.25
0.50
0.75
1.00
1.25
1.50
1.75
2.00
2.25
2.50
TOTAL POWER DISSIPATION (W)
Figure 86. Junction Temperature vs. Power Dissipation, TA = 25°C
140
130
120
110
100
90
6400mm2
500mm2
100mm2
TJ MAX
80
70
60
50
0
The device is soldered to minimum size pin traces.
0.25
0.50
0.75
1.00
1.25
1.50
1.75
2.00
TOTAL POWER DISSIPATION (W)
The junction temperature of the ADP2370/ADP2371 is
calculated from the following equation:
09531-087
1
θJA (°C/W)
162.2
124.1
68.7
56.5
42.4
125
Figure 87. Junction Temperature vs. Power Dissipation, TA = 50°C
145
TJ = TA + (PD × θJA)
(2)
PD = PBUCK = PSW + PTRAN + PSW_COND
(3)
where:
PSW, PTRAN, and PSW_COND are defined in the Efficiency section.
135
JUNCTION TEMPERATURE (°C)
where:
TA is the ambient temperature.
PD is the total power dissipation in the die, given by
125
115
105
95
6400mm2
500mm2
100mm2
TJ MAX
85
75
65
0
0.25
0.50
0.75
1.00
1.25
1.50
1.75
2.00
TOTAL POWER DISSIPATION (W)
Figure 88. Junction Temperature vs. Power Dissipation, TA = 65°C
Rev. D | Page 29 of 32
09531-088
Copper Size (mm2)
251
100
500
1000
6400
135
09531-086
To guarantee reliable operation, the junction temperature of the
ADP2370/ADP2371 must not exceed 125°C. To ensure the junction temperature stays below this maximum value, the user must
be aware of the parameters that contribute to junction temperature
changes. These parameters include ambient temperature, power
dissipation in the power device, and the thermal resistance between
the junction and ambient air (θJA). The θJA number is dependent
on the package assembly compounds that are used and the amount
of PCB copper soldered to the package GND and EPAD. Table 8
shows typical θJA values of the 8-lead, 3 mm × 3 mm LFCSP for
various PCB copper sizes.
145
JUNCTION TEMPERATURE (°C)
If the junction temperature of the ADP2370/ADP2371 exceeds
150°C, the regulator enters thermal shutdown. The regulator
recovers only after the junction temperature has fallen below
130°C, this helps to prevent any permanent damage to the IC.
Thermal analysis for the chosen application is clearly very
important to guarantee reliable operation under all conditions.
The junction temperature of the die is the sum of the ambient
temperature of the environment and the temperature rise of the
package due to the power dissipation, as shown in Equation 2.
For a given ambient temperature and total power dissipation,
there exists a minimum copper size requirement for the PCB to
ensure the junction temperature does not rise above 125°C. The
following figures (Figure 86 to Figure 89) show junction
temperature calculations for different ambient temperatures,
total power dissipation, and areas of PCB copper.
JUNCTION TEMPERATURE (°C)
In most applications, the ADP2370/ADP2371 do not dissipate
much heat due to their high efficiency. However, in applications
with high ambient temperature and high supply voltage-to-output
voltage differential, the heat dissipated in the package may be
large enough to cause the junction temperature of the die to
exceed the 125°C maximum.
ADP2370/ADP2371
Data Sheet
PCB LAYOUT CONSIDERATIONS
135
Improve heat dissipation from the package by increasing
the amount of copper attached to the pins of the ADP2370/
ADP2371. However, as listed in Table 8, a point of diminishing
returns is eventually reached, beyond which an increase in the
copper size does not yield significant heat dissipation benefits.
JUNCTION TEMPERATURE (°C)
125
115
Poor layout can affect the ADP2370/ADP2371 buck performance
causing electromagnetic interference (EMI), poor electromagnetic
compatibility (EMC) performance, ground bounce, and voltage
losses; thus, regulation and stability can be affected. Implement
a good PCB layout to ensure optimum performance by applying
the following rules:
105
85
0
0.2
0.4
0.6
0.8
1.0
TOTAL POWER DISSIPATION (W)
09531-089
6400mm2
500mm2
100mm2
TJ MAX
95
•
Figure 89. Junction Temperature vs. Power Dissipation, TA = 85°C
In cases where the board temperature is known, use the thermal
characterization parameter, ΨJB, to estimate the junction temperature rise. Maximum junction temperature (TJ) is calculated
from the board temperature (TB) and power dissipation (PD)
using the formula:
TJ = TB + (PD × ΨJB)
•
•
(5)
The typical ΨJB value for the 8-lead, 3 mm × 3 mm LFCSP is
22.2°C/W.
•
120
100
25°C
50°C
65°C
85°C
TJ MAX
80
60
40
20
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
TOTAL POWER DISSIPATION (W)
5.0
09531-090
JUNCTION TEMPERATURE (°C)
140
Figure 90. Junction Temperature vs. Power Dissipation,
Different Board Temperatures
Rev. D | Page 30 of 32
Place the inductor, input capacitor, and output capacitor
close to the IC using short tracks. These components carry
high switching frequencies and long, large tracks act like
antennas.
Route the output voltage path away from the inductor and
SW node to minimize noise and magnetic interference.
Use a ground plane with several vias connected to the
component-side ground to reduce noise interference on
sensitive circuit nodes.
Use of 0402-size or 0603-size capacitors achieves the smallest
possible footprint solution on boards where area is limited.
ADP2370/ADP2371
09531-091
Data Sheet
09531-092
Figure 91. PCB Layout, Top
Figure 92. PCB Layout, Bottom
Rev. D | Page 31 of 32
ADP2370/ADP2371
Data Sheet
PACKAGING AND ORDERING INFORMATION
OUTLINE DIMENSIONS
2.48
2.38
2.23
3.10
3.00 SQ
2.90
8
5
EXPOSED
PAD
TOP VIEW
SEATING
PLANE
4
1
BOTTOM VIEW
0.80 MAX
0.55 NOM
0.80
0.75
0.70
0.30
0.25
0.18
1.74
1.64
1.49
0.50 BSC
0.05 MAX
0.02 NOM
COPLANARITY
0.08
0.20 REF
0.20 MIN
PIN 1
INDICATOR
(R 0.2)
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
COMPLIANT TO JEDEC STANDARDS MO-229-WEED-4
02-05-2013-B
INDEX
AREA
0.50
0.40
0.30
Figure 93. 8-Lead Lead Frame Chip Scale Package [LFCSP_WD]
3 mm × 3 mm Body, Very Very Thin, Dual Lead
(CP-8-5)
Dimensions shown in millimeters
ORDERING GUIDE
Model 1
ADP2370ACPZ-1.2-R7
ADP2370ACPZ-1.5-R7
ADP2370ACPZ-1.8-R7
ADP2370ACPZ-2.5-R7
ADP2370ACPZ-3.0-R7
ADP2370ACPZ-3.3-R7
ADP2370ACPZ-5.0-R7
ADP2370ACPZ-R7
ADP2370ACPZ-R2
ADP2371ACPZ-1.2-R7
ADP2371ACPZ-1.8-R7
ADP2371ACPZ-3.3-R7
ADP2371ACPZ-R7
ADP2370CPZ-REDYKIT
1
Buck Output Voltage (V)
1.2
1.5
1.8
2.5
3.0
3.3
5.0
Adjustable
Adjustable
1.2 with QOD
1.8 with QOD
3.3 with QOD
Adjustable with QOD
Temperature Range
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
−40°C to +125°C
Z = RoHS Compliant Part.
©2012–2014 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D09531-0-2/14(D)
Rev. D | Page 32 of 32
Package Description
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
8-Lead LFCSP_WD
REDYKIT
Package Option
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
CP-8-5
Branding
LL4
LL5
LL6
LL7
LL8
LL9
LLB
LGZ
LGZ
LLJ
LLK
LLL
LLM