400 MHz to 6 GHz
Quadrature Demodulator
ADL5380
Data Sheet
FEATURES
FUNCTIONAL BLOCK DIAGRAM
ENBL
ADJ
ADL5380
IHI
BIAS
ILO
LOIP
RFIN
V2I
QUADRATURE
PHASE SPLITTER
RFIP
LOIN
QHI
QLO
07585-001
Operating RF and LO frequency: 400 MHz to 6 GHz
Input IP3
30 dBm at 900 MHz
28 dBm at 1900 MHz
Input IP2: >65 dBm at 900 MHz
Input P1dB (IP1dB): 11.6 dBm at 900 MHz
Noise figure (NF)
10.9 dB at 900 MHz
11.7 dB at 1900 MHz
Voltage conversion gain: ~7 dB
Quadrature demodulation accuracy at 900 MHz
Phase accuracy: ~0.2°
Amplitude balance: ~0.07 dB
Demodulation bandwidth: ~390 MHz
Baseband I/Q drive: 2 V p-p into 200 Ω
Single 5 V supply
Figure 1.
APPLICATIONS
Cellular W-CDMA/GSM/LTE
Microwave point-to-(multi)point radios
Broadband wireless and WiMAX
GENERAL DESCRIPTION
The ADL5380 is a broadband quadrature I-Q demodulator that
covers an RF/IF input frequency range from 400 MHz to 6 GHz.
With a NF = 10.9 dB, IP1dB = 11.6 dBm, and IIP3 = 29.7 dBm at
900 MHz, the ADL5380 demodulator offers outstanding dynamic
range suitable for the demanding infrastructure direct-conversion
requirements. The differential RF inputs provide a well-behaved
broadband input impedance of 50 Ω and are best driven from a
1:1 balun for optimum performance.
Excellent demodulation accuracy is achieved with amplitude
and phase balances of ~0.07 dB and ~0.2°, respectively. The
demodulated in-phase (I) and quadrature (Q) differential outputs
are fully buffered and provide a voltage conversion gain of ~7 dB.
The buffered baseband outputs are capable of driving a 2 V p-p
differential signal into 200 Ω.
Rev. B
The fully balanced design minimizes effects from second-order
distortion. The leakage from the LO port to the RF port is
<−50 dBm. Differential dc offsets at the I and Q outputs are
typically <20 mV. Both of these factors contribute to the
excellent IIP2 specification, which is >65 dBm.
The ADL5380 operates off a single 4.75 V to 5.25 V supply. The
supply current is adjustable by placing an external resistor from
the ADJ pin to either the positive supply, VS, (to increase supply
current and improve IIP3) or to ground (which decreases supply
current at the expense of IIP3).
The ADL5380 is fabricated using the Analog Devices, Inc.,
advanced silicon-germanium bipolar process and is available
in a 24-lead exposed paddle LFCSP.
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Technical Support
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ADL5380
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
LO Interface ................................................................................ 22
Applications ....................................................................................... 1
V-to-I Converter ........................................................................ 22
Functional Block Diagram .............................................................. 1
Mixers .......................................................................................... 22
General Description ......................................................................... 1
Emitter Follower Buffers ........................................................... 22
Revision History ............................................................................... 2
Bias Circuit .................................................................................. 22
Specifications..................................................................................... 3
Applications Information .............................................................. 23
Absolute Maximum Ratings............................................................ 5
Basic Connections ...................................................................... 23
ESD Caution .................................................................................. 5
Power Supply............................................................................... 23
Pin Configuration and Function Descriptions ............................. 6
Local Oscillator and RF Inputs ................................................. 24
Typical Performance Characteristics ............................................. 7
Baseband Outputs ...................................................................... 25
Low Band Operation .................................................................... 7
Error Vector Magnitude (EVM) Performance ........................... 25
Midband Operation ................................................................... 11
Low IF Image Rejection............................................................. 26
High Band Operation ................................................................ 14
Example Baseband Interface ..................................................... 27
Distributions for fLO = 900 MHz ............................................... 17
Characterization Setups ................................................................. 31
Distributions for fLO = 1900 MHz............................................. 18
Evaluation Board ............................................................................ 33
Distributions for fLO = 2700 MHz............................................. 19
Thermal Grounding and Evaluation Board Layout............... 35
Distributions for fLO = 3600 MHz............................................. 20
Outline Dimensions ....................................................................... 36
Distributions for fLO = 5800 MHz............................................. 21
Ordering Guide .......................................................................... 36
Circuit Description ......................................................................... 22
REVISION HISTORY
12/14—Rev. A to Rev. B
Changes to Figure 2 and Table 3 ..................................................... 6
Updated Outline Dimensions ....................................................... 36
Changes to Ordering Guide .......................................................... 36
7/13—Rev. 0 to Rev. A
Changes to Table 2 ............................................................................ 5
Deleted Local Oscillator (LO) Input Section .............................. 23
Changed RF Input Section to Local Oscillator and RF Inputs
Section .............................................................................................. 24
Added Figure 78, Figure 79, and Figure 82,
Renumbered Sequentially.............................................................. 24
Added Figure 83 and Figure 84 .................................................... 25
Changes to Evaluation Board Section and Figure 102 .............. 33
Changes to Table 5 and Figure 103 Caption ............................... 34
Deleted Figure 100, Figure 101, and Figure 102 ......................... 34
Updated Outline Dimensions ....................................................... 36
Changes to Ordering Guide .......................................................... 36
7/09—Revision 0: Initial Version
Rev. B | Page 2 of 36
Data Sheet
ADL5380
SPECIFICATIONS
VS = 5 V, TA = 25°C, fLO = 900 MHz, fIF = 4.5 MHz, PLO = 0 dBm, ZO = 50 Ω, unless otherwise noted. Baseband outputs differentially
loaded with 450 Ω. Loss of the balun used to drive the RF port was de-embedded from these measurements.
Table 1.
Parameter
OPERATING CONDITIONS
LO and RF Frequency Range
LO INPUT
Input Return Loss
LO Input Level
I/Q BASEBAND OUTPUTS
Voltage Conversion Gain
Demodulation Bandwidth
Quadrature Phase Error
I/Q Amplitude Imbalance
Output DC Offset (Differential)
Output Common Mode
0.1 dB Gain Flatness
Output Swing
Peak Output Current
POWER SUPPLIES
Voltage
Current
ENABLE FUNCTION
Off Isolation
Turn-On Settling Time
Turn-Off Settling Time
ENBL High Level (Logic 1)
ENBL Low Level (Logic 0)
DYNAMIC PERFORMANCE at RF = 900 MHz
Conversion Gain
Input P1dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
Noise Figure
Noise Figure Under Blocking Conditions
Condition
Min
Typ
0.4
LOIP, LOIN
LO driven differentially through a balun at 900 MHz
−6
QHI, QLO, IHI, ILO
450 Ω differential load on I and Q outputs at 900 MHz
200 Ω differential load on I and Q outputs at 900 MHz
1 V p-p signal, 3 dB bandwidth
At 900 MHz
0 dBm LO input at 900 MHz
Dependent on ADJ pin setting
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
VADJ ~ 4.8 V (set by 200 Ω from ADJ pin to VS)
VADJ ~ 2.4 V (ADJ pin open)
Differential 200 Ω load
Each pin
VS = VCC1, VCC2, VCC3
−10
0
Unit
6
GHz
+6
dB
dBm
6.9
5.9
390
0.2
0.07
±10
dB
dB
MHz
Degrees
dB
mV
VS − 2.5
VS − 2.8
VS − 1.2
37
2
12
V
V
V
MHz
V p-p
mA
4.75
1.5 kΩ from ADJ pin to VS; ENBL pin low
1.5 kΩ from ADJ pin to VS; ENBL pin high
Pin ENBL
Max
5.25
245
145
−70
45
950
ENBL high to low
ENBL low to high
2.5
1.7
V
mA
mA
dB
ns
ns
V
V
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
With a −5 dBm input interferer 5 MHz away
Rev. B | Page 3 of 36
6.9
11.6
−19
68
29.7
−52
−67
0.07
0.2
10.9
13.1
dB
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
ADL5380
Parameter
DYNAMIC PERFORMANCE at RF = 1900 MHz
Conversion Gain
Input P1dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
Noise Figure
Noise Figure Under Blocking Conditions
DYNAMIC PERFORMANCE at RF = 2700 MHz
Conversion Gain
Input P1dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
Noise Figure
DYNAMIC PERFORMANCE at RF = 3600 MHz
Conversion Gain
Input P1dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
Noise Figure
Noise Figure Under Blocking Conditions
DYNAMIC PERFORMANCE at RF = 5800 MHz
Conversion Gain
Input P1dB
RF Input Return Loss
Second-Order Input Intercept (IIP2)
Third-Order Input Intercept (IIP3)
LO to RF
RF to LO
IQ Magnitude Imbalance
IQ Phase Imbalance
Noise Figure
Noise Figure Under Blocking Conditions
Data Sheet
Condition
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
With a −5 dBm input interferer 5 MHz away
VADJ ~ 4 V (set by 1.5 kΩ from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
Min
Typ
Max
Unit
6.8
11.6
−13
61
27.8
−49
−77
0.07
0.25
11.7
14
dB
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
7.4
11
−10
54
28
−49
−73
0.07
0.5
12.3
dB
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
6.3
9.6
−11
48
21
−46
−72
0.14
1.1
14.2
16.2
dB
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
5.8
8.2
−7.5
44
20.6
−47
−62
0.07
−1.25
15.5
18.9
dB
dBm
dB
dBm
dBm
dBm
dBc
dB
Degrees
dB
dB
VADJ ~ 4.8 V (set by200 Ω from ADJ pin to VS)
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
With a −5 dBm input interferer 5 MHz away
VADJ ~ 2.4 V (ADJ pin left open)
RFIP, RFIN driven differentially through a balun
−5 dBm each input tone
−5 dBm each input tone
RFIN, RFIP terminated in 50 Ω
LOIN, LOIP terminated in 50 Ω
With a −5 dBm input interferer 5 MHz away
Rev. B | Page 4 of 36
Data Sheet
ADL5380
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
Supply Voltage: VCC1, VCC2, VCC3
LO Input Power
RF Input Power
Internal Maximum Power Dissipation
θJA1
θJC
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
1
Rating
5.5 V
13 dBm (re: 50 Ω)
15 dBm (re: 50 Ω)
1370 mW
53°C/W
2.5°C/W
150°C
−40°C to +85°C
−65°C to +125°C
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
ESD CAUTION
Per JDEC standard JESD 51-2. For information on optimizing thermal
impedance, see the Thermal Grounding and Evaluation Board Layout
section.
Rev. B | Page 5 of 36
ADL5380
Data Sheet
24
23
22
21
20
19
VCC3
GND3
RFIP
RFIN
GND3
ADJ
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
ADL5380
TOP VIEW
(Not to Scale)
18
17
16
15
14
13
GND3
GND2
QHI
QLO
GND2
VCC2
07585-002
PIN 1
INDICATOR
1
2
3
4
5
6
ENBL 7
GND4 8
LOIP 9
LOIN 10
GND4 11
NC 12
GND3
GND1
IHI
ILO
GND1
VCC1
NOTES
1. NC = NO CONNECT. DO NOT CONNECT TO THIS PIN.
2. THE EXPOSED PAD SHOULD BE CONNECTED TO A
LOW IMPEDANCE THERMAL AND ELECTRICAL
GROUND PLANE.
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No.
1, 2, 5, 8, 11, 14,
17, 18, 20, 23
3, 4, 15, 16
Mnemonic
GND1, GND2, GND3, GND4
Description
Ground Connect.
IHI, ILO, QLO, QHI
6, 13, 24
VCC1, VCC2, VCC3
7
ENBL
9, 10
LOIP, LOIN
12
19
NC
ADJ
21, 22
RFIN, RFIP
I Channel and Q Channel Mixer Baseband Outputs. These outputs have a 50 Ω differential
output impedance (25 Ω per pin). Each output pair can swing 2 V p-p (differential) into a
load of 200 Ω. The output 3 dB bandwidth is ~400 MHz.
Supply. Positive supply for LO, IF, biasing, and baseband sections. Decouple these pins to
the board ground using the appropriate-sized capacitors.
Enable Control. When pulled low, the part is fully enabled; when pulled high, the part is
partially powered down and the output is disabled.
Local Oscillator Input. Pins must be ac-coupled. A differential drive through a balun is
necessary to achieve optimal performance. Recommended balun is the Mini-Circuits®
TC1-1-13 for lower frequencies, the Johanson Technology 3600 balun for midband
frequencies, and the Johanson Technology 5400 balun for high band frequencies.
Balun choice depends on the desired frequency range of operation.
No Connect. Do not connect to this pin.
A resistor to VS that optimizes third-order intercept. For operation <3 GHz, RADJ = 1.5 kΩ.
For operation from 3 GHz to 4 GHz, RADJ = 200 Ω. For operation >5 GHz, RADJ = open.
See the Circuit Description section for more details.
RF Input. A single-ended 50 Ω signal can be applied differentially to the RF inputs through
a 1:1 balun. Recommended balun is the Mini-Circuits TC1-1-13 for lower frequencies, the
Johanson Technology 3600 balun for midband frequencies, and the Johanson Technology
5400 balun for high band frequencies. Balun choice depends on the desired frequency
range of operation.
Exposed Pad. The exposed pad should be connected to a low impedance thermal and
electrical ground plane.
EP
Rev. B | Page 6 of 36
Data Sheet
ADL5380
TYPICAL PERFORMANCE CHARACTERISTICS
VS = 5 V, TA = 25°C, LO drive level = 0 dBm, RF input balun loss is de-embedded, unless otherwise noted.
LOW BAND OPERATION
RF = 400 MHz to 3 GHz; Mini-Circuits TC1-1-13 balun on LO and RF inputs, 1.5 kΩ from the ADJ pin to VS.
1.0
18
TA = –40°C
TA = +25°C
TA = +85°C
14
0.8
0.6
INPUT P1dB
GAIN MISMATCH (dB)
GAIN (dB), IP1dB (dBm)
16
12
10
GAIN
8
0.4
0.2
0
–0.2
–0.4
6
–0.6
3000
07585-005
2800
2600
2400
2200
2000
1800
1600
1400
1200
1000
LO FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 3. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
80
800
400
3000
–1.0
07585-003
2600
2800
2200
2400
1800
2000
1600
1400
1200
800
1000
600
2
400
TA = –40°C
TA = +25°C
TA = +85°C
–0.8
600
4
Figure 5. IQ Gain Mismatch vs. LO Frequency
2
I CHANNEL
Q CHANNEL
1
70
BASEBAND RESPONSE (dB)
0
INPUT IP2
50
INPUT IP3 (I AND Q CHANNELS)
30
–2
–3
–4
–5
–6
3000
07585-004
2600
2800
2200
2400
1800
2000
1600
1400
–7
1200
800
1000
10
TA = –40°C
TA = +25°C
TA = +85°C
600
20
–1
–8
10
100
BASEBAND FREQUENCY (MHz)
LO FREQUENCY (MHz)
Figure 6. Normalized IQ Baseband Frequency Response
Figure 4. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
Rev. B | Page 7 of 36
1000
07585-006
40
400
IIP3, IIP2 (dBm)
60
ADL5380
Data Sheet
15
14
13
12
11
10
280
INPUT IP3
SUPPLY CURRENT (mA)
16
TA = –40°C
TA = +25°C
TA = +85°C
30
IIP3 (dBm) AND NOISE FIGURE (dB)
TA = –40°C
TA = +25°C
TA = +85°C
17
NOISE FIGURE (dB)
300
35
18
260
25
240
20
SUPPLY
CURRENT
15
220
200
10
NOISE FIGURE
5
180
9
0
160
1.0
1.5
3.0
2.5
2.0
3.5
07585-010
07585-007
2800
3000
2400
2600
2000
2200
1800
1600
1400
1200
1000
800
600
400
8
4.5
4.0
VADJ (V)
LO FREQUENCY (MHz)
Figure 7. Noise Figure vs. LO Frequency
Figure 10. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 900 MHz
QUADRATURE PHASE ERROR (Degrees)
4
25
23
3
21
NOISE FIGURE (dB)
2
1
0
–1
TA = –40°C
TA = +25°C
TA = +85°C
–2
15
13
1920MHz
11
920MHz
5
–30
07585-008
3000
Figure 8. IQ Quadrature Phase Error vs. LO Frequency
Figure 11. Noise Figure vs. Input Blocker Level, fLO = 900 MHz, fLO = 1900 MHz
(RF Blocker 5 MHz Offset)
75
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
70
IIP2, Q CHANNEL
16
65
14
IP1dB
55
NOISE FIGURE
8
50
45
GAIN
6
40
4
35
IIP3
2
30
25
–5
–4
–3
–2
–1
0
1
2
3
4
5
6
LO LEVEL (dBm)
07585-009
10
IIP3, IIP2 ( dBm)
60
12
60
18
IIP2, I CHANNEL
18
5
IIP2, Q CHANNEL
16
55
IIP2, I CHANNEL
50
14
NOISE FIGURE
45
12
IP1dB
10
40
GAIN
8
35
IIP3, IIP2 (dBm)
20
0
30
6
IIP3
25
4
2
–6
20
–5
–4
–3
–2
–1
0
1
2
LO LEVEL (dBm)
3
4
5
6
Figure 12. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 2700 MHz
Figure 9. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 900 MHz
Rev. B | Page 8 of 36
07585-012
2800
2400
2600
2200
2000
1800
1400
1600
1200
1000
800
600
400
LO FREQUENCY (MHz)
–20
–15
–10
–5
RF BLOCKER INPUT POWER (dBm)
–25
07585-011
7
–4
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
17
9
–3
0
–6
19
Data Sheet
ADL5380
35
0
TA = –40°C
TA = +25°C
TA = +85°C
IIP3 (dBm) AND NOISE FIGURE (dB)
30
–5
RETURN LOSS (dB)
25
INPUT IP3
20
15
10
NOISE FIGURE
–10
–15
–20
1.0
1.5
2.0
2.5
3.0
VADJ (V)
3.5
4.0
–25
07585-013
0
4.5
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
RF FREQUENCY (GHz)
Figure 16. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through TC1-1-13 Balun
80
–20
70
–30
60
–40
LEAKAGE (dBm)
50
900MHz: GAIN
900MHz: IP1dB
900MHz: IIP2, I CHANNEL
900MHz: IIP2, Q CHANNEL
2700MHz: GAIN
2700MHz: IP1dB
2700MHz: IIP2, I CHANNEL
2700MHz: IIP2, Q CHANNEL
40
30
20
–60
–70
–80
10
1
2
3
4
–100
VADJ (V)
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQUENCY (GHz)
Figure 14. Conversion Gain, IP1dB, and IIP2 vs.
VADJ, fLO = 900 MHz, fLO = 2700 MHz
–20
85
–30
80
30
IP1dB, IIP3 (dBm)
90
IIP3
25
75
IIP2
20
70
15
65
60
10
IP1dB
5
0
4.5
6.5
8.5
10.5
12.5
14.5
16.5
BASEBAND FREQUENCY (MHz)
–40
LEAKAGE (dBc)
35
I CHANNEL
Q CHANNEL
55
18.5
50
–50
–60
–70
–80
–90
07585-015
TA = –40°C
TA = +25°C
TA = +85°C
Figure 17. LO-to-RF Leakage vs. LO Frequency
IIP2, I AND Q CHANNELS (dBm)
40
07585-017
–90
07585-014
0
–50
Figure 15. IP1dB, IIP3, and IIP2 vs. Baseband Frequency
–100
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
RF FREQUENCY (GHz)
Figure 18. RF-to-LO Leakage vs. RF Frequency
Rev. B | Page 9 of 36
07585-018
GAIN (dB), IP1dB (dBm), IIP2
I AND Q CHANNELS (dBm)
Figure 13. IIP3 and Noise Figure vs. VADJ, fLO = 2700 MHz
07585-016
5
ADL5380
Data Sheet
0
–2
–6
–8
–10
–12
–14
–16
0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6 2.8 3.0
LO FREQUENCY (GHz)
07585-019
RETURN LOSS (dB)
–4
Figure 19. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through TC1-1-13 Balun
Rev. B | Page 10 of 36
Data Sheet
ADL5380
MIDBAND OPERATION
RF = 3 GHz to 4 GHz; Johanson Technology 3600BL14M050T balun on LO and RF inputs, 200 Ω from VADJ to VS.
12
IP1dB
11
10
9
8
GAIN
7
6
5
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
LO FREQUENCY (GHz)
3.8
3.9
4.0
18
Figure 20. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
16
14
40
IP1dB
10
35
8
30
GAIN
6
25
4
20
IIP3
2
15
–5
–4
–3
–2 –1
0
1
LO LEVEL (dBm)
2
3
4
5
6
10
Figure 23. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 3600 MHz
17
I CHANNEL
Q CHANNEL
16
NOISE FIGURE (dB)
INPUT IP2
60
50
40
INPUT IP3 I AND Q CHANNELS
15
14
13
12
TA = –40°C
TA = +25°C
TA = +85°C
11
10
20
3.1
3.2
3.3
3.4
3.5
3.6
3.7
LO FREQUENCY (GHz)
3.8
3.9
4.0
8
07585-021
3.0
3.1
3.2
3.3
3.4
3.5
3.6
3.7
LO FREQUENCY (GHz)
3.8
3.9
4.0
3.9
4.0
Figure 24. Noise Figure vs. LO Frequency
Figure 21. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
4
1.0
0.6
QUADRATURE PHASE ERROR (Degrees)
TA = –40°C
TA = +25°C
TA = +85°C
0.8
0.4
0.2
0
–0.2
–0.4
–0.6
–1.0
3.0
3.2
3.4
3.6
LO FREQUENCY (GHz)
3.8
4.0
07585-022
–0.8
TA = –40°C
TA = +25°C
TA = +85°C
3
2
1
0
–1
–2
–3
–4
3.0
3.1
3.2
3.4
3.6
3.3
3.5
3.7
LO FREQUENCY (GHz)
3.8
Figure 25. IQ Quadrature Phase Error vs. LO Frequency
Figure 22. IQ Gain Mismatch vs. LO Frequency
Rev. B | Page 11 of 36
07585-025
3.0
07585-024
9
10
GAIN MISMATCH (dB)
IIP3, IIP2 (dBm)
45
NOISE FIGURE
18
TA = –40°C
TA = +25°C
TA = +85°C
30
50
12
80
70
55
IIP2, Q CHANNEL
IIP2, I CHANNEL
0
–6
07585-020
4
60
IIP3, IIP2 (dBm)
TA = –40°C
TA = +25°C
TA = +85°C
13
GAIN (dB), IP1dB (dBm)
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
20
07585-023
14
ADL5380
Data Sheet
300
–20
280
–30
20
260
–40
15
240
TA = –40°C
TA = +25°C
TA = +85°C
25
10
NOISE FIGURE
5
220
LEAKAGE (dBm)
INPUT IP3
CURRENT (mA)
IIP3 (dBm) AND NOISE FIGURE (dB)
30
–50
–60
200
–70
180
–80
2.0
1.5
2.5
3.0
3.5
4.0
4.5
VADJ (V)
3.1
3.2
3.3
3.4
3.5
3.6
3.7
LO FREQUENCY (GHz)
3.8
3.9
4.0
07585-029
0
1.0
07585-026
SUPPLY CURRENT
Figure 29. LO-to-RF Leakage vs. LO Frequency
Figure 26. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 3600 MHz
–20
25
–30
23
LEAKAGE (dBc)
19
17
15
–50
–60
–70
–80
13
–90
–25
–20
–15
–10
–5
0
5
RF POWEL LEVEL (dBm)
–100
07585-027
11
–30
3.1
3.2
3.3
3.4
3.5
3.6
3.7
RF FREQUENCY (GHz)
3.8
3.9
4.0
3.9
4.0
07585-030
NOISE FIGURE (dB)
–40
21
Figure 30. RF-to-LO Leakage vs. RF Frequency
Figure 27. Noise Figure vs. Input Blocker Level, fLO = 3600 MHz
(RF Blocker 5 MHz Offset)
0
80
70
RETURN LOSS (dB)
GAIN (dB), IP1dB (dBm), IIP2
I AND Q CHANNELS (dBm)
–2
60
50
40
3600MHz: GAIN
3600MHz: IP1dB
3600MHz: IIP2, I CHANNEL
3600MHz: IIP2, Q CHANNEL
30
20
–4
–6
–8
10
–10
1
2
3
4
V ADJ (V)
–12
3.1
3.2
3.3
3.4
3.5
3.6
3.7
RF FREQUENCY (GHz)
3.8
07585-031
–10
07585-028
0
Figure 31. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
Figure 28. Conversion Gain, IP1dB, and IIP2 vs. VADJ, fLO = 3600 MHz
Rev. B | Page 12 of 36
Data Sheet
ADL5380
0
RETURN LOSS (dB)
–5
–10
–15
–20
–30
3.1
3.2
3.3
3.4
3.5
3.6
3.7
LO FREQUENCY (GHz)
3.8
3.9
4.0
07585-032
–25
Figure 32. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 3600 Balun
Rev. B | Page 13 of 36
ADL5380
Data Sheet
HIGH BAND OPERATION
RF = 5 GHz to 6 GHz; Johanson Technology 5400BL15B050E balun on LO and RF inputs, the ADJ pin is open.
8
7
GAIN
6
5
TA = –40°C
TA = +25°C
TA = +85°C
4
3
5.1
5.2
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
6.0
Figure 33. Conversion Gain and Input 1 dB Compression Point (IP1dB) vs.
LO Frequency
16
50
45
14
IIP2, I CHANNEL
12
10
40
35
IP1dB
30
8
GAIN
6
4
25
20
IIP3
2
15
0
–6
–5
–4
–3
–2 –1
0
1
LO LEVEL (dBm)
2
3
4
5
6
10
Figure 36. Conversion Gain, IP1dB, Noise Figure, IIP3, and IIP2 vs.
LO Level, fLO = 5800 MHz
20
80
TA = –40°C
TA = +25°C
TA = +85°C
70
18
17
NOISE FIGURE (dB)
INPUT IP2
50
40
INPUT IP3 (I AND Q CHANNELS)
30
TA = –40°C
TA = –25°C
TA = +85°C
19
I CHANNEL
Q CHANNEL
60
IIP3, IIP2 (dBm)
55
NOISE FIGURE
IIP2, Q CHANNEL
IIP3, IIP2 (dBm)
INPUT P1dB
9
18
07585-036
GAIN (dB), IP1dB (dBm), NOISE FIGURE (dB)
10
07585-033
GAIN (dB), INPUT P1dB (dBm)
11
2
60
20
12
16
15
14
13
12
11
10
20
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
6.0
8
07585-034
5.2
5.0
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
6.0
4
1.0
TA = –40°C
TA = +25°C
TA = +85°C
0.6
3
IQ PHASE MISMATCH (Degrees)
0.8
0.4
0.2
0
–0.2
–0.4
–0.6
TA = –40°C
TA = +25°C
TA = +85°C
2
1
0
–1
–2
5.1
5.2
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
6.0
Figure 35. IQ Gain Mismatch vs. LO Frequency
–4
5.1
5.2
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
Figure 38. IQ Quadrature Phase Error vs. LO Frequency
Rev. B | Page 14 of 36
6.0
07585-038
–3
–0.8
07585-035
IQ AMPLITUDE MISMATCH (dB)
5.2
Figure 37. Noise Figure vs. LO Frequency
Figure 34. Input Third-Order Intercept (IIP3) and
Input Second-Order Intercept Point (IIP2) vs. LO Frequency
–1.0
5.1
07585-037
9
10
5.1
Data Sheet
ADL5380
300
TA = –40°C
TA = +25°C
TA = +85°C
INPUT IP3
20
–30
280
–40
260
NOISE FIGURE
15
240
10
220
LEAKAGE (dBm)
25
–20
CURRENT (mA)
IIP3 (dBm) AND NOISE FIGURE (dB)
30
–50
–60
–70
–80
SUPPLY CURRENT
200
5
180
1.5
2.0
2.5
3.0
3.5
4.0
–10 0
5.1
07585-039
0
1.0
4.5
VADJ (V)
5.2
5.3
5.4
5.5
5.6
5.7
LO FREQUENC Y (GHz)
5.8
5.9
6.0
5.9
6.0
07585-042
–90
Figure 42. LO-to-RF Leakage vs. LO Frequency
Figure 39. IIP3, Noise Figure, and Supply Current vs. VADJ, fLO = 5800 MHz
–20
25
–30
20
LEAKAGE (dBc)
NOISE FIGURE (dB)
–40
15
10
–50
–60
–70
–80
5
–25
–20
–15
–10
RF POWER LEVEL (dBm)
–5
–100
07585-040
0
–30
5.1
Figure 40. Noise Figure vs. Input Blocker Level, fLO = 5800 MHz
(RF Blocker 5 MHz Offset)
5.3
5.4
5.5
5.6
5.7
RF FREQUENCY (MHz)
5.8
Figure 43. RF-to-LO Leakage vs. RF Frequency
60
0
–2
50
RETURN LOSS (dB)
–4
40
5800MHz: GAIN
5800MHz: IP1dB
5800MHz: IIP2, I CHANNEL
5800MHz: IIP2, Q CHANNEL
30
20
–6
–8
–10
–12
10
0
1
2
3
4
VADJ (V)
–16
5.1
Figure 41. Conversion Gain, IP1dB, and IIP2 vs.
RBIAS, fLO = 5800 MHz
5.2
5.3
5.4
5.5
5.6
5.7
RF FREQUENCY (GHz)
5.8
5.9
6.0
07585-044
–14
07585-041
GAIN (dB), IP1dB (dBm), IIP2
I AND Q CHANNEL (dBm)
5.2
07585-043
–90
Figure 44. RF Port Return Loss vs. RF Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
Rev. B | Page 15 of 36
ADL5380
Data Sheet
–0
–2
RETURN LOSS (dB)
–4
–6
–8
–10
–12
–16
5.1
5.2
5.3
5.4
5.5
5.6
5.7
LO FREQUENCY (GHz)
5.8
5.9
6.0
07585-045
–14
Figure 45. LO Port Return Loss vs. LO Frequency Measured on
Characterization Board Through Johanson Technology 5400 Balun
Rev. B | Page 16 of 36
Data Sheet
ADL5380
100
90
90
DISTRIBUTION PERCENTAGE (%)
100
80
70
60
50
40
30
TA = –40°C
TA = +25°C
TA = +85°C
10
28
29
30
31
32
INPUT IP3 (dBm)
70
50
40
30
20
10
33
34
0
45
50
60
65
70
INPUT IP2 (dBm)
75
80
85
100
100
IP1dB
GAIN
90
80
70
60
50
40
30
20
TA = –40°C
TA = +25°C
TA = +85°C
0
4
5
6
7
8
9
10
11
GAIN (dB), IP1dB (dBm)
70
60
50
40
30
TA = –40°C
TA = +25°C
TA = +85°C
20
10
12
13
14
0
9.5
07585-047
10
80
10.0
100
90
90
DISTRIBUTION PERCENTAGE (%)
100
80
70
60
50
40
30
TA = –40°C
TA = +25°C
TA = +85°C
0
–0.3
–0.2
–0.1
0
0.1
GAIN MISMATCH (dB)
12.5
TA = –40°C
TA = +25°C
TA = +85°C
80
70
60
50
40
30
20
10
0.2
0.3
07585-048
10
12.0
Figure 50. Noise Figure Distributions
Figure 47. Gain and IP1dB Distributions
20
10.5
11.0
11.5
NOISE FIGURE (dB)
07585-050
DISTRIBUTION PERCENTAGE (%)
90
DISTRIBUTION PERCENTAGE (%)
55
Figure 49. IIP2 Distributions for I Channel and Q Channel
Figure 46. IIP3 Distributions
DISTRIBUTION PERCENTAGE (%)
I CHANNEL
Q CHANNEL
60
0
–1.0
–0.8
–0.6 –0.4 –0.2
0
0.2
0.4
0.6
QUADRATURE PHASE ERROR (Degrees)
0.8
Figure 51. IQ Quadrature Phase Error Distributions
Figure 48. IQ Gain Mismatch Distributions
Rev. B | Page 17 of 36
1.0
07585-051
0
TA = –40°C
TA = +25°C
TA = +85°C
80
07585-049
20
07585-046
DISTRIBUTION PERCENTAGE (%)
DISTRIBUTIONS FOR fLO = 900 MHz
ADL5380
Data Sheet
100
90
90
DISTRIBUTION PERCENTAGE (%)
100
80
70
60
50
40
30
TA = –40°C
TA = +25°C
TA = +85°C
10
24
25
80
60
50
40
30
20
10
26
27
28
29
INPUT IP3 (dBm)
30
31
32
0
45
Figure 52. IIP3 Distributions
50
60
65
INPUT IP2 (dBm)
70
75
80
100
TA = –40°C
TA = +25°C
TA = +85°C
90
IP1dB
GAIN
70
60
50
40
30
20
10
80
70
60
50
40
30
20
TA = –40°C
TA = +25°C
TA = +85°C
10
4
5
6
7
8
9
10
11
12
13
14
GAIN (dB), IP1dB (dBm)
0
10.5
07585-053
0
11.0
12.0
12.5
13.0
13.5
NOISE FIGURE (dB)
Figure 53. Gain and IP1dB Distributions
Figure 56. Noise Figure Distributions
100
100
90
TA = –40°C
TA = +25°C
TA = +85°C
90
DISTRIBUTION PERCENTAGE (%)
TA = –40°C
TA = +25°C
TA = +85°C
80
70
60
50
40
30
20
80
70
60
50
40
30
20
10
–0.2
–0.1
0
0.1
GAIN MISMATCH (dB)
0.2
0.3
07585-054
10
0
–0.3
11.5
07585-056
80
DISTRIBUTION PERCENTAGE (%)
90
DISTRIBUTION PERCENTAGE (%)
55
Figure 55. IIP2 Distributions for I Channel and Q Channel
100
DISTRIBUTION PERCENTAGE (%)
I CHANNEL
Q CHANNEL
70
0
–1.0
–0.8
–0.6 –0.4 –0.2
0
0.2
0.4
0.6
QUADRATURE PHASE ERROR (Degrees)
0.8
Figure 57. IQ Quadrature Phase Error Distributions
Figure 54. IQ Gain Mismatch Distributions
Rev. B | Page 18 of 36
1.0
07585-057
0
TA = –40°C
TA = +25°C
TA = +85°C
07585-055
20
07585-052
DISTRIBUTION PERCENTAGE (%)
DISTRIBUTIONS FOR fLO = 1900 MHz
Data Sheet
ADL5380
100
100
90
90
DISTRIBUTION PERCENTAGE (%)
80
70
60
50
40
TA = –40°C
TA = +25°C
TA = +85°C
30
20
10
20
22
24
26
28
30
INPUT IP3 (dBm)
32
34
36
60
50
40
30
20
0
35
40
50
55
60
INPUT IP2 (dBm)
65
70
75
100
90
IP1dB
GAIN
80
TA = –40°C
TA = +25°C
TA = +85°C
90
DISTRIBUTION PERCENTAGE (%)
TA = –40°C
TA = +25°C
TA = +85°C
70
60
50
40
30
20
10
80
70
60
50
40
30
20
5
6
7
8
9
10
11
GAIN (dB), IP1dB (dBm)
12
13
14
0
10.5
07585-059
4
11.0
90
90
DISTRIBUTION PERCENTAGE (%)
100
80
70
60
50
40
30
0
–0.3
TA = –40°C
TA = +25°C
TA = +85°C
–0.2
–0.1
0
0.1
GAIN MISMATCH (dB)
13.5
14.0
80
2.0
TA = –40°C
TA = +25°C
TA = +85°C
70
60
50
40
30
20
10
0.2
0.3
07585-060
10
12.0
12.5
13.0
NOISE FIGURE (dB)
Figure 62. Noise Figure Distributions
100
20
11.5
07585-062
10
Figure 59. Gain and IP1dB Distributions
DISTRIBUTION PERCENTAGE (%)
45
Figure 61. IIP2 Distributions for I Channel and Q Channel
100
DISTRIBUTION PERCENTAGE (%)
70
07585-061
18
Figure 58. IIP3 Distributions
0
80
10
07585-058
0
I CHANNEL
Q CHANNEL
TA = –40°C
TA = +25°C
TA = +85°C
07585-063
DISTRIBUTION PERCENTAGE (%)
DISTRIBUTIONS FOR fLO = 2700 MHz
Figure 60. IQ Gain Mismatch Distributions
0
–2.0
–1.5
–1.0
–0.5
0
0.5
1.0
QUADRATURE PHASE ERROR (Degrees)
1.5
Figure 63. IQ Quadrature Phase Error Distributions
Rev. B | Page 19 of 36
ADL5380
Data Sheet
100
100
90
90
DISTRIBUTION PERCENTAGE (%)
80
70
60
TA = –40°C
TA = +25°C
TA = +85°C
50
40
30
20
80
70
60
50
40
30
20
15
17
19
21
23
25
27
INPUT IP3 (dBm)
29
31
33
0
07585-064
0
35
Figure 64. IIP3 Distributions
45
50
55
INPUT IP2 (dBm)
60
65
70
Figure 67. IIP2 Distributions for I Channel and Q Channel
100
100
IP1dB
GAIN
80
TA = –40°C
TA = +25°C
TA = +85°C
70
60
TA = –40°C
TA = +25°C
TA = +85°C
90
DISTRIBUTION PERCENTAGE (%)
90
50
40
30
20
10
80
70
60
50
40
30
20
10
4
5
6
7
8
9
10
11
GAIN (dB), IP1dB (dBm)
12
13
14
0
12.5
07585-065
0
Figure 65. Gain and IP1dB Distributions
13.5
14.0
14.5
15.0
NOISE FIGURE (dB)
15.5
16.0
2.5
Figure 68. Noise Figure Distributions
100
100
90
DISTRIBUTION PERCENTAGE (%)
70
TA = –40°C
TA = +25°C
TA = +85°C
90
TA = –40°C
TA = +25°C
TA = +85°C
80
60
50
40
30
20
10
80
70
60
50
40
30
20
10
–0.2
–0.1
0
0.1
GAIN MISMATCH (dB)
0.2
0.3
07585-066
0
–0.3
13.0
07585-068
DISTRIBUTION PERCENTAGE (%)
40
07585-067
10
10
DISTRIBUTION PERCENTAGE (%)
I CHANNEL
Q CHANNEL
TA = –40°C
TA = +25°C
TA = +85°C
07585-069
DISTRIBUTION PERCENTAGE (%)
DISTRIBUTIONS FOR fLO = 3600 MHz
Figure 66. IQ Gain Mismatch Distributions
0
–0.5
0
0.5
1.0
1.5
2.0
QUADRATURE PHASE ERROR (Degrees)
Figure 69. IQ Quadrature Phase Error Distributions
Rev. B | Page 20 of 36
Data Sheet
ADL5380
DISTRIBUTIONS FOR fLO = 5800 MHz
100
100
TA = –40°C
TA = +25°C
TA = +85°C
80
90
DISTRIBUTION PERCENTAGE (%)
70
60
50
40
30
20
10
70
60
50
40
30
20
21
22
INPUT IP3 (dBm)
23
24
0
30
40
45
50
55
INPUT IP2 (dBm)
60
65
70
Figure 73. IIP2 Distributions for I Channel and Q Channel
100
100
TA = –40°C
TA = +25°C
TA = +85°C
80
90
DISTRIBUTION PERCENTAGE (%)
90
IP1dB
GAIN
70
60
50
40
30
20
10
TA = –40°C
TA = +25°C
TA = +85°C
80
70
60
50
40
30
20
3
4
5
6
7
GAIN (dB), IP1dB (dBm)
8
9
10
0
13.0
07585-071
2
14.0
14.5
15.0
15.5
16.0
16.5
17.0
17.5
18.0
NOISE FIGURE (dB)
Figure 74. Noise Figure Distributions
100
100
90
90
DISTRIBUTION PERCENTAGE (%)
TA = –40°C
TA = +25°C
TA = +85°C
80
70
60
50
40
30
20
80
TA = –40°C
TA = +25°C
TA = +85°C
70
60
50
40
30
20
10
–0.2
–0.1
0
0.1
GAIN MISMATCH (dB)
0.2
0.3
07585-072
10
0
–0.3
13.5
07585-074
10
Figure 71. Gain and IP1dB Distributions
DISTRIBUTION PERCENTAGE (%)
35
07585-073
20
07585-070
19
Figure 70. IIP3 Distributions
DISTRIBUTION PERCENTAGE (%)
80
10
0
18
0
I CHANNEL
Q CHANNEL
TA = –40°C
TA = +25°C
TA = +85°C
0
–3
–2
–1
0
1
2
QUADRATURE PHASE ERROR (Degrees)
Figure 75. IQ Quadrature Phase Error Distributions
Figure 72. IQ Gain Mismatch Distributions
Rev. B | Page 21 of 36
3
07585-075
DISTRIBUTION PERCENTAGE (%)
90
ADL5380
Data Sheet
CIRCUIT DESCRIPTION
The ADL5380 can be divided into five sections: the local
oscillator (LO) interface, the RF voltage-to-current (V-to-I)
converter, the mixers, the differential emitter follower outputs,
and the bias circuit. A detailed block diagram of the device is
shown in Figure 76.
ENBL
ADJ
ADL5380
IHI
BIAS
ILO
LOIP
RFIN
QUADRATURE
PHASE SPLITTER
V2I
RFIP
Table 4. ADJ Pin Resistor Values and Approximate ADJ Pin
Voltages
RADJ
200 Ω to VS
600 Ω to VS
1.54 kΩ to VS
3.8 kΩ to VS
10 kΩ to VS
Open
9 kΩ to GND
3.5 kΩ to GND
1.5 kΩ to GND
~VADJ (V)
4.8
4.5
4
3.5
3
2.5
2
1.5
1
~ Baseband CommonMode Output (V)
2.2
2.3
2.5
2.7
3
3.2
3.4
3.6
3.8
MIXERS
LOIN
The ADL5380 has two double-balanced mixers: one for the inphase channel (I channel) and one for the quadrature channel
(Q channel). These mixers are based on the Gilbert cell design
of four cross-connected transistors. The output currents from
the two mixers are summed together in the resistive loads that
then feed into the subsequent emitter follower buffers.
QLO
07585-076
QHI
EMITTER FOLLOWER BUFFERS
Figure 76. Block Diagram
The LO interface generates two LO signals at 90° of phase
difference to drive two mixers in quadrature. RF signals are
converted into currents by the V-to-I converters that feed into
the two mixers. The differential I and Q outputs of the mixers
are buffered via emitter followers. Reference currents to each
section are generated by the bias circuit. A detailed description
of each section follows.
The output emitter followers drive the differential I and Q signals
off chip. The output impedance is set by on-chip 25 Ω series
resistors that yield a 50 Ω differential output impedance for
each baseband port. The fixed output impedance forms a
voltage divider with the load impedance that reduces the effective
gain. For example, a 500 Ω differential load has 1 dB lower
effective gain than a high (10 kΩ) differential load impedance.
LO INTERFACE
BIAS CIRCUIT
The LO interface consists of a polyphase quadrature splitter
followed by a limiting amplifier. The LO input impedance is set
by the polyphase, which splits the LO signal into two differential
signals in quadrature. The LO input impedance is nominally
50 Ω. Each quadrature LO signal then passes through a limiting
amplifier that provides the mixer with a limited drive signal. For
optimal performance, the LO inputs must be driven differentially.
A band gap reference circuit generates the reference currents
used by different sections. The bias circuit can be enabled and
partially disabled using ENBL (Pin 7). If ENBL is grounded or
left open, the part is fully enabled. Pulling ENBL high shuts off
certain sections of the bias circuitry, reducing the standing
power to about half of its fully enabled consumption and
disabling the outputs.
V-TO-I CONVERTER
The differential RF input signal is applied to a V-to-I converter
that converts the differential input voltage to output currents.
The V-to-I converter provides a differential 50 Ω input impedance.
The V-to-I bias current can be adjusted up or down using the
ADJ pin (Pin 19). Adjusting the current up improves IIP3 and
IP1dB but degrades SSB NF. Adjusting the current down improves
SSB NF but degrades IIP3 and IP1dB. The current adjustment
can be made by connecting a resistor from the ADJ pin (Pin 19)
to VS to increase the bias current or to ground to decrease the
bias current. Table 4 approximately dictates the relationship
between the resistor used (RADJ), the resulting ADJ pin voltage,
and the resulting baseband common-mode output voltage.
Rev. B | Page 22 of 36
Data Sheet
ADL5380
APPLICATIONS INFORMATION
BASIC CONNECTIONS
electrical impedance ground plane. If the ground plane spans
multiple layers on the circuit board, these layers should be stitched
together with nine vias under the exposed paddle. The AN-772
Application Note discusses the thermal and electrical grounding of
the LFCSP in detail. Decouple each of the supply pins using two
capacitors; recommended capacitor values are 100 pF and 0.1 µF.
Figure 77 shows the basic connections schematic for the ADL5380.
POWER SUPPLY
The nominal voltage supply for the ADL5380 is 5 V and is
applied to the VCC1, VCC2, and VCC3 pins. Connect ground
to the GND1, GND2, GND3, and GND4 pins. Solder the exposed
paddle on the underside of the package to a low thermal and
RFIN
BALUN
100pF
100pF
RADJ
VS
VS
22
21
20
RFIN
GND3
GND3
GND3 18
2 GND1
GND2 17
3 IHI
IHI
19
ADJ
23
RFIP
1
24
GND3
100pF
VCC3
0.1µF
QHI 16
QHI
ADL5380
4 ILO
7
VCC2 13
8
9
10
11
12
100pF
NC
GND4
6 VCC1
100pF
LOIN
GND2 14
LOIP
QLO
VS
100pF
0.1µF
100pF
BALUN
LO_SE
Figure 77. Basic Connections Schematic
Rev. B | Page 23 of 36
07585-078
0.1µF
5 GND1
GND4
VS
QLO 15
ENBL
ILO
ADL5380
Data Sheet
LO INPUT
The RF and LO inputs have a differential input impedance of
approximately 50 Ω as shown in Figure 78. Figure 79 shows the
return loss. For optimum performance, both the LO and RF ports
should be ac-coupled and driven differentially through a balun as
shown in Figure 80 and Figure 81. The user has many different
types of balun to choose from and from a variety of manufacturers.
For the data presented in this data sheet all measurements were
gathered with the baluns listed below. For applications that are
band specific, the recommended baluns are:
2.0
60
0
RESISTANCE
–0.5
40
–1.0
20
1400
2400
3400
4400
5400
100
90
80
RF AND LO PORTS DIFFERENITAL DRIVE:
TCM1-63AX+
70
60
50
40
30
RF AND LO PORTS SINGLE-ENDED DRIVE
20
–2.0
6400
RF FREQUENCY (MHz)
10
0
400
Figure 78. Differential Input Impedance of the RF Port
1400
2400
3400
FREQUENCY (MHz)
–8
4400
5400
Figure 82. IIP2 vs. Frequency Comparison for Single-Ended and Differential
Drive of the RF and LO Ports
–10
–12
–14
–16
–18
–20
–22
–24
–26
–28
–30
0
0.5
1.0
1.5
2.0 2.5 3.0 3.5 4.0
RF FREQUENCY (GHz)
4.5
5.0
5.5
6.0
07585-080
DIFFERENTIAL RETURN LOSS RF PORT (dB)
RFIP
Alternatively, if the single-ended drive of both the LO and RF ports
is the desired mode of operation, degradations in IIP2 will be
observed because of the lack of common mode rejection. The
degradation in IIP2 is more prevalent at high frequencies,
specifically frequencies greater than 1600 MHz. At low frequencies,
the ADL5380 has inherent common mode rejection offering
superior IIP2 performance in the 70 dBm range. As shown in
Figure 82 and Figure 83, in single-ended mode, the largest
performance impact is seen in IIP2 while minimal performance
degradation is observed in IIP3.
–1.5
0
400
22
100pF
07585-179
0.5
RFIN
BALUN
07585-178
PARALLEL RIN (Ω)
CAPACITANCE
80
21
100pF
PARALLEL CAPACITANCE (pF)
1.5
1.0
Figure 80. Differential LO Drive
07585-079
The recommended drive level for the LO port is between −6 dBm
and +6 dBm.
100
LOIN
Figure 81. RF Input
For wideband applications covering the entire 400 MHz to 6 GHz
range of the ADL5380, the recommended balun is the TCM163AX+ from Mini-Circuits. This wide and maximally flat balun
allows coverage of the entire frequency range with one component.
120
10
RF INPUT
Up to 3 GHz is the Mini-Circuits TC1-1-13.
From 3 GHz to 4 GHz is the Johanson Technology
3600BL14M050.
From 4.9 GHz to 6 GHz is the Johanson Technology
5400BL15B050.

LOIP
100pF
IIP2 (dBm)


9
100pF
BALUN
07585-077
LOCAL OSCILLATOR AND RF INPUTS
Figure 79. Differential RF Port Return Loss
Rev. B | Page 24 of 36
Data Sheet
ADL5380
40
ERROR VECTOR MAGNITUDE (EVM) PERFORMANCE
RF AND LO PORTS DIFFERENITAL
DRIVE: TCM1-63AX+
EVM is a measure used to quantify the performance of a digital
radio transmitter or receiver. A signal received by a receiver has all
constellation points at their ideal locations; however, various
imperfections in the implementation (such as magnitude
imbalance, noise floor, and phase imbalance) cause the actual
constellation points to deviate from their ideal locations.
30
IIP3 (dBm)
25
20
RF AND LO PORTS SINGLE-ENDED DRIVE
15
10
0
400
1400
2400
3400
4400
07585-180
5
5400
FREQUENCY (MHz)
Figure 83. IIP3 vs. Frequency Comparison for Single-Ended and Differential
Drive of the RF and LO Ports
To configure the ADL5380 for single-ended drive, terminate the
unused input with a 100 pF capacitor to GND while driving the
alternative input. The single-ended input impedance is 25 Ω or
half the differential impedance. As a result of this, ensure that
there is proper impedance matching when interfacing with the
ADL5380 in single-ended mode for maximum transfer of
power. Figure 84, shows an example single ended configuration
when using a signal source with a 50 Ω source impedance.
In general, a demodulator exhibits three distinct EVM limitations
vs. received input signal power. At strong signal levels, the
distortion components falling in-band due to nonlinearities in
the device cause strong degradation to EVM as signal levels
increase. At medium signal levels, where the demodulator behaves
in a linear manner and the signal is well above any notable noise
contributions, the EVM has a tendency to reach an optimum
level determined dominantly by the quadrature accuracy of the
demodulator and the precision of the test equipment. As signal
levels decrease, such that noise is a major contribution, the EVM
performance vs. the signal level exhibits a decibel-for-decibel
degradation with decreasing signal level. At lower signal levels,
where noise proves to be the dominant limitation, the decibel
EVM proves to be directly proportional to the SNR.
The ADL5380 shows excellent EVM performance for various
modulation schemes. Figure 86 shows the EVM performance of
the ADL5380 with a 16 QAM, 200 kHz low IF.
IHI
0
ILO
25Ω
RFIP
LOIP
–5
25Ω
0°
RFIN
–10
LOIN
90°
100pF
–15
100pF
07585-181
QLO
EVM (dB)
QHI
Figure 84. Single-Ended Configuration
The baseband outputs QHI, QLO, IHI, and ILO are fixed
impedance ports. Each baseband pair has a 50 Ω differential
output impedance. The outputs can be presented with differential
loads as low as 200 Ω (with some degradation in gain) or high
impedance differential loads (500 Ω or greater impedance yields
the same excellent linearity) that is typical of an ADC. The
TCM9-1 9:1 balun converts the differential IF output to a singleended output. When loaded with 50 Ω, this balun presents a 450 Ω
load to the device. The typical maximum linear voltage swing for
these outputs is 2 V p-p differential. The output 3 dB bandwidth
is 390 MHz. Figure 85 shows the baseband output configuration.
3
16
QHI
15
QLO
4
07585-081
ADL5380
ILO
–25
–30
–35
BASEBAND OUTPUTS
IHI
–20
Figure 85. Baseband Output Configuration
Rev. B | Page 25 of 36
–40
–45
–50
–90
–70
–50
–30
RF INPUT POWER (dBm)
–10
Figure 86. EVM, RF = 900 MHz, IF = 200 kHz vs.
RF Input Power for a 16 QAM 160ksym/s Signal
10
07585-082
35
ADL5380
Data Sheet
–10
Figure 87 shows the zero-IF EVM performance of a 10 MHz
IEEE 802.16e WiMAX signal through the ADL5380. The
differential dc offsets on the ADL5380 are in the order of a few
millivolts. However, ac coupling the baseband outputs with 10 µF
capacitors eliminates dc offsets and enhances EVM performance.
With a 10 MHz BW signal, 10 µF ac coupling capacitors with
the 500 Ω differential load results in a high-pass corner frequency
of ~64 Hz, which absorbs an insignificant amount of modulated
signal energy from the baseband signal. By using ac coupling
capacitors at the baseband outputs, the dc offset effects, which
can limit dynamic range at low input power levels, can be
eliminated.
–15
EVM (dB)
–20
–30
0Hz IF
–35
2.5MHz LOW-IF
5MHz LOW-IF
–40
–70
–60
–50
–40
–30
–20
RF INPUT POWER (dBm)
–10
0
10
07585-084
7.5MHz LOW-IF
–45
–80
0
EVM (dB)
–25
–10
Figure 88. EVM, RF = 1900 MHz, IF = 0 Hz, IF = 2.5 MHz, IF = 5 MHz, and IF =
7.5 MHz vs. RF Input Power for a W-CDMA Signal (AC-Coupled Baseband Outputs)
–20
LOW IF IMAGE REJECTION
–30
5.8GHz
–40
3.5GHz
–50
–65
–55
–45
–35
–25
–15
–5
RF INPUT POWER (dBm)
5
07585-083
2.6GHz
–60
–75
Figure 87. EVM, RF = 2.6 GHz, RF = 3.5 GHz, and RF = 5.8 GHz, IF = 0 Hz vs.
RF Input Power for a 16 QAM 10 MHz Bandwidth Mobile WiMAX Signal
(AC-Coupled Baseband Outputs)
The image rejection ratio is the ratio of the intermediate
frequency (IF) signal level produced by the desired input
frequency to that produced by the image frequency. The image
rejection ratio is expressed in decibels. Appropriate image rejection
is critical because the image power can be much higher than
that of the desired signal, thereby plaguing the down-conversion
process. Figure 89 illustrates the image problem. If the upper
sideband (lower sideband) is the desired band, a 90° shift to the Q
channel (I channel) cancels the image at the lower sideband
(upper sideband). Phase and gain balance between I and Q
channels are critical for high levels of image rejection.
Figure 88 exhibits multiple W-CDMA low-IF EVM performance
curves over a wide RF input power range into the ADL5380. In
the case of zero-IF, the noise contribution by the vector signal
analyzer becomes predominant at lower power levels, making it
difficult to measure SNR accurately.
COSωLOt
ωIF
0°
ωIF
–ωIF
0
+ωIF
–90°
0
+ωIF
0
+ωIF
+90°
ωLO
ωUSB
0°
–ωIF
0
+ωIF
07585-085
ωLSB
SINωLOt
Figure 89. Illustration of the Image Problem
Rev. B | Page 26 of 36
Data Sheet
ADL5380
Figure 90 and Figure 91 show the excellent image rejection
capabilities of the ADL5380 for low IF applications, such as
W-CDMA. The ADL5380 exhibits image rejection greater than
45 dB over a broad frequency range.
60
2.5MHz LOW IF
5MHz LOW IF
7MHz LOW IF
40
30
20
0
400
07585-103
10
800
1200
1600 2000 2400 2800
RF FREQUENCY (MHz)
3200 3600
4000
Figure 90. Low Band and Midband Image Rejection vs. RF Frequency for a
W-CDMA Signal, IF = 2.5 MHz, 5 MHz, and 7.5 MHz
As an example, a second-order Butterworth, low-pass filter design
is shown in Figure 92 where the differential load impedance is
500 Ω and the source impedance of the ADL5380 is 50 Ω. The
normalized series inductor value for the 10-to-1, load-to-source
impedance ratio is 0.074 H, and the normalized shunt capacitor
is 14.814 F. For a 10.9 MHz cutoff frequency, the single-ended
equivalent circuit consists of a 0.54 μH series inductor followed
by a 433 pF shunt capacitor.
60
IMAGE REJECTION (dB)
50
40
30
The order and type of filter network depends on the desired high
frequency rejection required, pass-band ripple, and group delay.
Filter design tables provide outlines for various filter types and
orders, illustrating the normalized inductor and capacitor values
for a 1 Hz cutoff frequency and 1 Ω load. After scaling the
normalized prototype element values by the actual desired
cut-off frequency and load impedance, the series reactance
elements are halved to realize the final balanced filter network
component values.
2.5MHz LOW IF
5MHz LOW IF
7MHz LOW IF
The balanced configuration is realized as the 0.54 μH inductor
is split in half to realize the network shown in Figure 92.
20
10
07585-104
0
5000
RS = 50Ω
5200
5400
5600
RF FREQUENCY (MHz)
5800
NORMALIZED
SINGLE-ENDED
CONFIGURATION
VS
6000
CN
14.814F
RS
= 0.1
RL
Figure 91. High Band Image Rejection vs. RF Frequency for a W-CDMA Signal,
IF = 2.5 MHz, 5 MHz, and 7.5 MHz
RS = 50Ω
EXAMPLE BASEBAND INTERFACE
In most direct-conversion receiver designs, it is desirable to
select a wanted carrier within a specified band. The desired
channel can be demodulated by tuning the LO to the appropriate
carrier frequency. If the desired RF band contains multiple
carriers of interest, the adjacent carriers are also down converted to
a lower IF frequency. These adjacent carriers can be problematic if
they are large relative to the wanted carrier because they can
overdrive the baseband signal detection circuitry. As a result, it
is often necessary to insert a filter to provide sufficient rejection
of the adjacent carriers.
LN = 0.074H
fC = 1Hz
0.54µH
DENORMALIZED
SINGLE-ENDED
EQUIVALENT
VS
RS
= 25Ω
2
RS
= 25Ω
2
433pF
RL= 500Ω
fC = 10.9MHz
0.27µH
BALANCED
CONFIGURATION
VS
RL= 500Ω
433pF
RL
2 = 250Ω
RL
= 250Ω
2
0.27µH
Figure 92. Second-Order Butterworth, Low-Pass Filter Design Example
Rev. B | Page 27 of 36
07585-087
IMAGE REJECTION (dB)
50
It is necessary to consider the overall source and load impedance
presented by the ADL5380 and ADC input when designing the
filter network. The differential baseband output impedance of
the ADL5380 is 50 Ω. The ADL5380 is designed to drive a high
impedance ADC input. It may be desirable to terminate the
ADC input down to lower impedance by using a terminating
resistor, such as 500 Ω. The terminating resistor helps to better
define the input impedance at the ADC input at the cost of a
slightly reduced gain (see the Circuit Description section for
details on the emitter-follower output loading effects).
ADL5380
Data Sheet
10
800
700
600
500
400
300
200
100
0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
1.6
FREQUENCY (MHz)
Figure 94. Sixth-Order Baseband Filter Group Delay
0
–5
–10
–15
–20
0
0.5
1.0
1.5
2.0
2.5
3.0
FREQUENCY (MHz)
3.5
07585-088
MAGNITUDE RESPONSE (dB)
5
Figure 93. Sixth-Order Baseband Filter Response
Rev. B | Page 28 of 36
1.8
07585-089
Figure 93 and Figure 94 show the measured frequency response
and group delay of the filter.
900
DELAY (ns)
A complete design example is shown in Figure 95. A sixth-order
Butterworth differential filter having a 1.9 MHz corner frequency
interfaces the output of the ADL5380 to that of an ADC input.
The 500 Ω load resistor defines the input impedance of the
ADC. The filter adheres to typical direct conversion W-CDMA
applications where, 1.92 MHz away from the carrier IF frequency,
1 dB of rejection is desired, and, 2.7 MHz away from the carrier IF
frequency, 10 dB of rejection is desired.
Data Sheet
ADL5380
RFIN
BALUN
100pF
100pF
VS
VS
23
22
21
20
GND3
RFIP
RFIN
GND3
1 GND3
19
ADJ
24
VCC3
100pF
0.1µF
GND3 18
2 GND1
GND2 17
3 IHI
QHI 16
ADL5380
4 ILO
NC
7
GND4
VCC2 13
LOIN
6 VCC1
100pF
LOIP
GND2 14
GND4
0.1µF
5 GND1
ENBL
VS
QLO 15
8
9
10
11
12
100pF
VS
100pF
0.1µF
100pF
BALUN
LO_SE
27µH
27µH
10µH
270pF
100pF
68pF
CAC
10µF
CAC
10µF
27µH
27µH
27µH
27µH
10µH
10µH
500Ω
CAC
10µF
270pF
100pF
68pF
27µH
27µH
10µH
500Ω
ADC INPUT
ADC INPUT
Figure 95. Sixth-Order Low-Pass Butterworth, Baseband Filter Schematic
Rev. B | Page 29 of 36
07585-090
CAC
10µF
ADL5380
Data Sheet
5
0
200Ω
1.5µH
–5
–10
–15
–20
–25
–30
–40
1.5µH
0
07585-091
2.2µH
5
10
15
20
25
30
35
40
FREQUENCY (MHz)
07585-092
–35
Figure 97. Fourth-Order Low-Pass LTE Filter Magnitude Response
Figure 96. Fourth-Order Low-Pass LTE Filter Schematic
60
GROUP DELAY (ns)
50
40
30
20
10
0
0
5
10
15
20
25
FREQUENCY (MHz)
30
35
40
07585-093
22pF
100pF
50Ω
2.2µH
Figure 97 and Figure 98 illustrate the magnitude response and
group delay response of the fourth-order filter, respectively.
FREQUENCY RESPONSE (dB)
As the load impedance of the filter increases, the filter design
becomes more challenging in terms of meeting the required
rejection and pass band specifications. In the previous W-CDMA
example, the 500 Ω load impedance resulted in the design of a
sixth-order filter that has relatively large inductor values and small
capacitor values. If the load impedance is 200 Ω, the filter design
becomes much more manageable. Figure 96 shows a fourth-order
filter designed for a 10 MHz wide LTE signal. As shown in
Figure 96, the resultant inductor and capacitor values become
much more practical with a 200 Ω load.
Figure 98. Fourth-Order Low-Pass LTE Filter Group Delay Response
Rev. B | Page 30 of 36
Data Sheet
ADL5380
CHARACTERIZATION SETUPS
The two setups shown in Figure 99 and Figure 100 were used
for making NF measurements. Figure 99 shows the setup for
measuring NF with no blocker signal applied while Figure 100
was used to measure NF in the presence of a blocker. For both
setups, the noise was measured at a baseband frequency of
10 MHz. For the case where a blocker was applied, the output
blocker was at a 15 MHz baseband frequency. Note that great
care must be taken when measuring NF in the presence of a
blocker. The RF blocker generator must be filtered to prevent
its noise (which increases with increasing generator output power)
from swamping the noise contribution of the ADL5380. At least
30 dB of attention at the RF and image frequencies is desired.
For example, assume a 915 MHz signal applied to the LO inputs of
the ADL5380. To obtain a 15 MHz output blocker signal, the RF
blocker generator is set to 930 MHz and the filters tuned such
that there is at least 30 dB of attenuation from the generator at
both the desired RF frequency (925 MHz) and the image RF
frequency (905 MHz). Finally, the blocker must be removed
from the output (by the 10 MHz low-pass filter) to prevent
the blocker from swamping the analyzer.
Figure 99 to Figure 101 show the general characterization bench
setups used extensively for the ADL5380. The setup shown in
Figure 101 was used to do the bulk of the testing and used
sinusoidal signals on both the LO and RF inputs. An automated
Agilent VEE program was used to control the equipment over
the IEEE bus. This setup was used to measure gain, IP1dB, IIP2,
IIP3, I/Q gain match, and quadrature error. The ADL5380
characterization board had a 9-to-1 impedance transformer on
each of the differential baseband ports to do the differential-tosingle-ended conversion, which presented a 450 Ω differential load
to each baseband port, when interfaced with 50 Ω test equipment.
For all measurements of the ADL5380, the loss of the RF input
balun was de-embedded. Due to the wideband nature of the
ADL5380, three different board configurations had to be used to
characterize the product. For low band characterization (400 MHz
to 3 GHz), the Mini-Circuits TC1-1-13 balun was used on the
RF and LO inputs to create differential signals at the device pins.
For midband characterization (3 GHz to 4 GHz), the Johanson
Technology 3600BL14M050T was used, and for high band
characterization (5 GHz to 6 GHz), the Johanson Technology
5400BL15B050E balun was used.
SNS
OUTPUT
RF
ADL5380
VPOS CHAR BOARD
I
LO
INPUT
6dB PAD
HP 6235A
POWER SUPPLY
R1
50Ω
AGILENT N8974A
NOISE FIGURE ANALYZER
LOW-PASS
FILTER
IEEE
GND
Q
FROM SNS PORT
CONTROL
AGILENT 8665B
SIGNAL GENERATOR
PC CONTROLLER
Figure 99. General Noise Figure Measurement Setup
Rev. B | Page 31 of 36
07585-095
IEEE
ADL5380
Data Sheet
BAND-PASS
TUNABLE FILTER
BAND-REJECT
TUNABLE FILTER
6dB PAD
R&S SMT03
SIGNAL GENERATOR
RF
GND
ADL5380
6dB PAD
VPOS CHAR BOARD
LOW-PASS
FILTER
I
LO
6dB PAD
HP 6235A
POWER SUPPLY
R&S FSEA30
SPECTRUM ANALYZER
R1
50Ω
Q
HP 87405
LOW NOISE
PREAMP
07585-096
BAND-PASS
CAVITY FILTER
AGILENT 8665B
SIGNAL GENERATOR
Figure 100. Measurement Setup for Noise Figure in the Presence of a Blocker
3dB PAD
RF
AMPLIFIER
3dB PAD IN
RF
OUT 3dB PAD
IEEE
VP GND
3dB PAD
AGILENT
11636A
R&S SMT06
6dB PAD
IEEE
RF
SWITCH
MATRIX
VPOS CHAR BOARD
LO
I 6dB PAD
IEEE
6dB PAD
AGILENT E3631
POWER SUPPLY
RF
INPUT
AGILENT E8257D
SIGNAL GENERATOR
IEEE
PC CONTROLLER
IEEE
R&S FSEA30
SPECTRUM ANALYZER
Figure 101. General Characterization Setup
Rev. B | Page 32 of 36
HP 8508A
VECTOR VOLTMETER
07585-097
IEEE
Q 6dB PAD
ADL5380
IEEE
RF
GND
INPUT CHANNELS
A AND B
R&S SMT06
Data Sheet
ADL5380
EVALUATION BOARD
The board can be used for single-ended or differential baseband
analysis. The default configuration of the board is for single-ended
baseband analysis.
The ADL5380 evaluation board is available. The evaluation board
is populated with the wide band TCM1-63AX+ transformer
from Mini-Circuits. This transformer covers the entire
frequency range of the ADL5380 from 400 MHz to 6 GHZ.
RFx
T3x
C5x
C12x
R19x
R23x
VPOS
R5x
IPx
23
22
21
20
19
GND3
RFIP
RFIN
GND3
ADJ
C11x
24
VCC3
VPOS
C8x
1
GND3
GND3 18
2
GND1
GND2 17
R3x
QPx
R16x
3
T4x
C16x
QHI 16
IHI
R6x
ADL5380
R7x
4
ILO
5
GND1
QLO 15
R15x
R4x
R13x
QNx
R10x
R2x
R12x
VCC2 13
R9x
GND4
7
8
9
10
11
VPOS
C7x
C10x
NC
LOIN
VCC1
LOIP
6
C6x
GND4
VPOS
C9x
T2x
C15x
GND2 14
ENBL
INx
R18x
R14x
12
R1x
R11x
VPOS
C2x
C3x
C4x
C1x
P1x
T1x
VPOS
LONx
LOPx
LO_SE
Figure 102. Evaluation Board Schematic
Rev. B | Page 33 of 36
07585-098
R17x
ADL5380
Data Sheet
Table 5. Evaluation Board Configuration Options
Component
VPOSx, GNDx
R10x, R12x,
R19x
C6x to C11x
Description
Power Supply and Ground Vector Pins.
Power Supply Decoupling. Shorts or power supply decoupling resistors.
Default Condition
Not applicable
R10x, R12x, R19x = 0 Ω (0603)
The capacitors provide the required dc coupling up to 6 GHz.
P1x, R11x,
R9x, R1x
R23x
Device Enable. When connected to VS, the device is active.
C6x, C7x, C8x = 100 pF (0402),
C9x, C10x, C11x = 0.1 µF (0603)
P1x, R9x = DNI, R1x = DNI,
R11x = 0 Ω
R23x = 1.5 kΩ (0603)
T2x, T4x
C15x, C16x
T1x
T3x
07585-099
C1x to C5x,
C12x
R2x to R7x,
R13x to R18x
Adjust Pin. The resistor value here sets the bias voltage at this pin and optimizes
third-order distortion.
AC Coupling Capacitors. These capacitors provide the required ac coupling
from 400 MHz to 4 GHz.
Single-Ended Baseband Output Path. This is the default configuration of the
evaluation board. R13x to R18x are populated for appropriate balun interface.
R2x to R5x are not populated. Baseband outputs are taken from QHI and IHI. The
user can reconfigure the board to use full differential baseband outputs. R2x to R5x
provide a means to bypass the 9:1 TCM9-1 transformer to allow for differential baseband outputs. Access the differential baseband signals by populating R2x to R5x
with 0 Ω and not populating R13x to R18x. This way the transformer does not need
to be removed. The baseband outputs are taken from the SMAs of QHI, QLO, IHI,
and ILO. R6x and R7x are provisions for applying a specific differential load across
the baseband outputs
IF Output Interface. TCM9-1 converts a differential high impedance IF output to
a single-ended output. When loaded with 50 Ω, this balun presents a 450 Ω load
to the device. The center tap can be decoupled through a capacitor to ground.
Decoupling Capacitors. C15x and C16x are the decoupling capacitors used to reject
noise on the center tap of the TCM9-1.
LO Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
RF Input Interface. A 1:1 RF balun that converts the single-ended RF input to
differential signal is used.
Figure 103. Evaluation Board Top Layer
Rev. B | Page 34 of 36
C1x, C4x = DNI,
C2x, C3x, C5x, C12x = 100 pF (0402)
R2x to R7x = open,
R13x to R18x = 0 Ω (0402)
T2x, T4x = TCM9-1, 9:1 (Mini-Circuits)
C15x, C16x = 0.1 µF (0402)
TCM1-63AX+
TCM1-63AX+
Data Sheet
ADL5380
12 mil.
THERMAL GROUNDING AND EVALUATION
BOARD LAYOUT
The package for the ADL5380 features an exposed paddle on the
underside that should be well soldered to a low thermal and
electrical impedance ground plane. This paddle is typically
soldered to an exposed opening in the solder mask on the
evaluation board. Figure 104 illustrates the dimensions used in
the layout of the ADL5380 footprint on the ADL5380 evaluation
board (1 mil = 0.0254 mm).
25 mil.
23 mil.
82 mil.
Notice the use of nine via holes on the exposed paddle. These
ground vias should be connected to all other ground layers on
the evaluation board to maximize heat dissipation from the
device package.
12 mil.
98.4 mil.
133.8 mil.
07585-105
19.7 mil.
Figure 104. Dimensions for Evaluation Board Layout for the ADL5380 Package
Under these conditions, the thermal impedance of the ADL5380
was measured to be approximately 30°C/W in still air.
Rev. B | Page 35 of 36
ADL5380
Data Sheet
OUTLINE DIMENSIONS
0.30
0.25
0.18
0.50
BSC
PIN 1
INDICATOR
24
19
18
1
EXPOSED
PAD
2.65
2.50 SQ
2.45
13
TOP VIEW
0.80
0.75
0.70
0.50
0.40
0.30
6
12
BOTTOM VIEW
0.05 MAX
0.02 NOM
COPLANARITY
0.08
SEATING
PLANE
7
0.25 MIN
FOR PROPER CONNECTION OF
THE EXPOSED PAD, REFER TO
THE PIN CONFIGURATION AND
FUNCTION DESCRIPTIONS
SECTION OF THIS DATA SHEET.
0.20 REF
COMPLIANT TO JEDEC STANDARDS MO-220-WGGD.
03-11-2013-A
PIN 1
INDICATOR
4.10
4.00 SQ
3.90
Figure 105. 24-Lead Lead Frame Chip Scale Package [LFCSP_WQ]
4 mm × 4 mm Body, Very Very Thin Quad
(CP-24-7)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
ADL5380ACPZ-R7
ADL5380ACPZ-WP
ADL5380-EVALZ
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
Package Description
24-Lead LFCSP_WQ
24-Lead LFCSP_WQ
Z = RoHS Compliant Part.
©2009–2014 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D07585-0-12/14(B)
Rev. B | Page 36 of 36
Package Option
CP-24-7
CP-24-7
Ordering Quantity
1,500, 7” Tape and Reel
64, Waffle Pack
1