Analog Circuit Design on Digital CMOS Why it is difficult, and which ideas help. Presented by HP. Schmid. Background on Hanspeter Schmid – Dissertation on video-frequency integrated filters (ETH Zürich) – Analog IC Designer at Bernafon / William Demant Holding: – Analog electronics: LNAs, amplifiers, regulators, filters, standard cells, circuits for wireless communication system. – System design, analog signal processing and signal integrity. – Communication facilitator between Danish and Swiss Teams. – IME: research projects (sensor systems, sigma-delta, etc.), consulting, teaching. – ETH Zürich: teaching analog (integrated) signal processing – IEEE CAS: – Chair Analog Signal Processing Tech. Comm. – Associate Editor of TCAS-I – Hobbies: going for walks, playing trombone, reading. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 2 Tutorial Philosophy © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 3 Philosophy I: Be a fool! – multiparameter optimization – – – – – – – – – noise distortion power consumption signal delay chip area offset yield mask costs … – conscious vs. subconscious – conscious mind: 4…5 criteria – subconscious: 100? 200? – what it means to be a fool © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 4 Philosophy II: Be a child – open for everything – playful – does not do what she should do – a child has got time! – Advice for scientists by Douglas Adams: See first, think later, then test. But always see first, or you will only see what you expect to see! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 5 Philosophy III: Be a climber – works hard to achieve a goal – is well trained – normally gets to the intended goal – Is the intention good? The direct path leads only to the goal! Gide) new The most exciting phrase in science, the one (André that heralds discoveries, is not Eureka! (I found it!), but – Will That's funny ... the fool not fall down? (Isaac Asimov) Not if the fool also is a child. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 6 Tutorial Contents Image from http://www.beatenbergbilder.ch/ © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 7 Introduction: What is new? – More metal layers – Small lateral distances – Thinner gates – more C – less Vdd – less gain – more weak inversion Image from http://www.ndl.org.tw/cht/ndlcomm/P10_2/7.pdf © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 8 Multi-metal cross section Example: 6 Metal layers. Lateral dimensions are smaller than vertical dimensions! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 9 Transconductance in Strong and Weak Inversion Strong Inversion Weak Inversion Moderate Inversion: Superposition © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 10 Maximum gain of single stage is reached in weak inversion For a given supply current: gain is proportional to supply voltage! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 11 Weak inversion = matching problems? For a 0.25u process: Voltage offset for identical supply current Current offset for identical gate-source voltage Therefore: Differential pairs in weak inversion Therefore: Current mirrors in strong inversion © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland from [Kinget07] ISCAS 2009 12 Summary – Thinner gates (and higher gate tunnelling currents!) – more gate (overlap, ...) capacitance per area – No buried channels anymore Æ pMOS is not better anymore in terms of flicker noise! – Less supply voltage Æ less signal – Less gain – same white noise at same supply current; less flicker noise – Sub-threshold leakage © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 13 Literature: What is new? [Annema99] Anne-Johan Annema, "Analog Circuit Performance and Process Scaling", IEEE Trans. Circuits and Systems—II, vol. 46, no. 6, pp. 711–725, June 1999. [Huang98] Qiuting Huang et. al., "The Impact of Scaling Down to Deep Submicron on CMOS RF Circuits," IEEE J. Solid-State Circuits, vol. 33, no. 7, pp. 1023–1036, July 1998 [Kinget07] Peter Kinget, "Device Mismatch: An Analog Design Perspective", ISCAS, New Orleans, pp. 1245–1248, May 2007. [Tsividis02] Yannis Tsividis, Mixed Analog-Digital VLSI Devices and Technology, World Scientific Publishers, 2002. [Tsividis99] Yannis Tsividis, Operation and Modelling of the MOS Transistor, ed. 2, McGraw-Hill 1999. [Dijksterhuis06] Ap Dijksterhuis et. al., "On Making the Right Choice: The DeliberationWithout-Attention Effect," Science, vol. 311, pp. 1005–1007, 2006. [Simons99] Daniel Simons et. al., "Gorillas in our midst: sustained inattentional blindness for dynamic events," Perception, vol. 28, pp. 1059–1074, 1999. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 14 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 15 Signal Integrity – Ground and Power Routing – Star Connections – Tapered Stars – Signal Grounds and Refs – Improving PSR (theory) – Finger capacitors and MIM-capacitors – Demodulation by nonlinearity – Decoupling © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 16 Why correct ground and power routing are important © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 17 On PCB: Power plane? No! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 18 On PCB: Split ground plane? Dangerous! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 19 Recommendations for PCB routing [National05] recommend – Use a single, unified ground plane – use separate power planes for analog and digital – let trace routing control ground currents. Low-power low-noise circuits: require controlled power/gnd routing! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 20 The problem of the star connection on chip © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 21 Calculation example: hearing aid system © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 22 16μΩ is not a lot! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 23 Solution: Tapered star This means: we have full control of where the noise currents flow. But: more chip area or more supply / ground wire resistance! Paradox: most sensitive nodes are farthest away from pad. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 24 Local decoupling is sometimes needed The question is: where shall the decoupling capacitor go? Answer: to the reference of the signal! But this may not be so easy. Many "PSR problems" are really coupling problems or problems with dirty references © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 25 How to improve PSRR and CMRR in a system? CMRR and PSRR are connected! Proof: Gauge transformation from [Säckinger91] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 26 Solution: Additional input from quiet ground Now we have one more degree of freedom © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 27 Example: additional signal path from [Loikkanen06] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 28 Example: additional signal path © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 29 Recommendations for chip routing Use "tapered" star connections For every differential signal node, make sure that the signal is referred to a clean signal. Input reference Problem: the references can change within a single circuit Output reference © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 30 Multi-metal Finger-Cap MIM-Cap combination © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 31 Comparison for a six-metal 0.18um CMOS process MIM capacitor (Metal 5 and Metal 6): 1.0 fF/μm2 Finger structure (Metal 1 … Metal 4): 1.3 fF/um2 MIM capacitor on top of Finger structure (all Metal): 2.3 fF/um2 MOSFET gate capacitance (non-linear): 10.0 fF/um2 Can we use a MOSFET gate capacitor for decoupling? © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 32 Demodulation by a nonlinearity I: DC offset Normal Operation with HF-Signal on Pad (weak inversion) Gives DC Offset! Inputs must be protected against this ... © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 33 Demodulation by a nonlinearity II: receiver Normal Operation with amplitude-modulated HF-Signal on Pad (weak inversion) Demodulates the signal and gives more DC offset! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 34 Realistic? Yes! In all digitally driven class-D (PWM) amplifiers, the signal is amplitude-modulated on the system clock frequency. The square of this signal appears in the supply current. If this strays back into a high-gain audio system: huge distortion or even instability! Solution: decouple all inputs ... to the respective reference of the signal ... as close to the pad as possible ... with as big a capacitor as possible © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 35 Literature: Signal Integrity [Loikkanen06] Mikko Loikkanen et. al., "PSRR Improvement Technique for Amplifiers with Miller Capacitor," ISCAS 2006, Kos, Greece, pp. 1394–1397. [National05] National Semiconductor Analog University, Meeting Signal-Path Design Challenges, High-performance seminar series 2005, part no. 570012-001. (Can be ordered from National for free.) [Säckinger91] Eduard Säckinger et. al., "A General Relationship Between Amplifier Parameters, And Its Application to PSRR Improvement," IEEE Trans. Circuits and Systems—I, vol. 38, no. 10, pp. 1173–1181, Oct 1991 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 36 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 37 An amp within an amp – Weak inversion – Zero-Vgs amplifiers – Super-Transistors – Cascode current mirrors – Self-biased cascodes – Regulated cascodes – Matryoshka amplifiers – Regulated cascode OTAs – Nested Miller amplifiers Image from http://www.souvenironline24.de/shop.aspx © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 38 Weak Inversion = Sub-threshold Operation from [Tsividis99] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 39 Zero-Vgs folded-cascode opamp in 0.18μm technology © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 40 Zero-Vgs folded-cascode opamp in 0.18μm technology VGS VT=230 mV (!), L=min, ID=5uA © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 41 Maximum gain of single stage is reached in weak inversion For a given supply current: gain is proportional to supply voltage! Less gain on (deep) submicron © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 42 Normal current mirror Output resistance Increase this with feedback! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 43 Cascode current mirror Feedback loop: For a constant signal current, the transistor M4 tries to keep the drain voltage of M2 constant. The loop gain around M4 is and the output resistance: Problem: high voltage drop. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 44 Low-voltage cascode current mirror Same feedback loop! Careful design needed such that M3 and M1 are always saturated Bias voltage necessary © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 45 Self-biased low-voltage cascode current mirror Still same feedback loop! But: for the same current, Vgs3 < Vgs1! – M1, M2 in strong inversion M3, M4 in weak inversion (makes Aloop small and M3,M4 huge) – M1, M2 normal-Vt transistors M3, M4 low-Vt transistors (requires low-Vt transistors, which most submicron processes have) © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 46 Different view: build super transistors Then: build good super transistors! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 47 The regulated cascode Increasing the loop gain ... ... gives much higher output resistance © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 48 The "original" by Säckinger simplest loop amplifier, but needs a lot of supply voltage from [Säckinger90] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 49 Matryoshka-style regulated-cascode amplifier several OTA Slices © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland one OTA Slice from [Treichler06] ISCAS 2009 50 Matryoshka slice layout! One OTA Slice Full OTA [Treichler06] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 51 Matryoshka Miller OpAmp: Two stages from [Huijsing01] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 52 Matryoshka Miller OpAmp: Three stages © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 53 Matryoshka Miller OpAmp: Four stages © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 54 Conclusion On modern digital technologies, we lose – supply voltage – gain If we need gain: – we need to combine more gain stages – and, if possible, use weak inversion Intuitive way to think about it: An Amp within an Amp within an Amp © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 55 Literature: New uses of old parts [Burger96] Thomas Burger and Qiuting Huang, "A 100dB 480MHz OTA in 0.7um CMOS for sampled-data applications," Proc. CICC, pp. 101–104, 1996. [Huijsing01] Johan H. Huijsing, Operational Amplifiers—Theory and Design, Kluwer Academic Publishers, 2001. [Säckinger90] Eduard Säckinger et. al, "A High-Swing, High-Impedance MOS Cascode Circuit," IEEE J. Solid-State Circuits, vol. 25, no. 1, pp. 289–298, Feb 1990. [Treichler06] Jürg Treichler et. al., "A 10-bit ENOB 50-MS/s Pipeline ADC in 130-nm CMOS at 1.2 V Supply," Proc. ESSCIRC, Montreux, Switzerland, pp. 552–555, 2006. [Tsividis99] Yannis Tsividis, Operation and Modelling of the MOS Transistor, ed. 2, McGraw-Hill 1999. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 56 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 57 Switched capacitors – Speed limit of SC filters – SC noise filtering – Switches and T-gates – Voltage doublers – for clock signals – for OTA tails – for control voltages – Flicker Noise – Autozero, CDS and Chopping © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 58 Simple SC resistor Pole frequency of SC resistor loaded with capacitance: from [Gregorian86] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 59 SC becomes much faster on modern processes from [Johns97] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 60 Huge SC resistor for noise filtering "Bucket Chain" technique Possible: 1s time constant! Requires RC filters for antialiasing e.g., 80fF, 160kHz, 13 elements Æ 1 GΩ Beware of offset!!! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 61 Bad Layout: asymmetries of clock lines! This can give huge offset. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 62 Good Layout: as symmetrical as possible © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 63 Types of switches from [Johns97] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 64 Voltage-level limitation © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 65 Benefitting from Narrow-Channel Effects from [Tsividis96] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 66 Reduce switch threshold voltage by slicing VT=610mV 0.18u Process Normal-VT Transistors VT=540mV © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 67 Clock voltage doubler "Doubling" pMOS gate voltages below VSS is also possible! from [Basu99] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 68 What is flicker noise? © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 69 Fllicker noise comes from a process with memory! from [Keshner82] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 70 Why is it called "flicker" noise? © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 71 On flicker noise: the Yahoo Aaaaaargh! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 72 On flicker noise: the Yahoo Aaaaaargh! from [Schmid07] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 73 Nature of Memory in MOSFETs Mainly interface traps at the channel-to-oxide and gate-to-oxide interfaces: – Spectrum caused by a single trap with time constant τ: – Distribution of the time constants: – Flicker noise slope is a physical property. – Flicker noise magnitude is related to the absolute number of interface traps. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 74 Model of scaling-invariant memory from [Schmid08] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 75 RMS behaviour of flicker noise © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 76 Reducing flicker noise by deleting memory I from [Klumperink00] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 77 Sampling noise from [Schmid08] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 78 Reducing offset and flicker noise by auto-zeroing Autozero 1: Vos 2: Vin+Vos 2−1: Vin Correlated Double Sampling 1: −Vin+Vos 2: Vin+Vos 2−1: 2Vin from [Enz96] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 79 Reducing offset and flicker noise by auto-zeroing © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 80 Reducing offset and flicker noise by chopping from [Enz96] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 81 Simulated chopped noise © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 82 Chopper circuit from [Schmid08] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 83 Matryoshka Chopper from [Schmid08] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 84 Multipath Chopper Chopped High Gain © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 85 Reducing offset and 1/f noise by correlated double sampling – Auto-zeroing: sample offset in one phase; sample signal in other phase while compensating offset. Auto-zeroing works in sampled time. – Chopping: modulate input signal to a higher frequency; modulate signal back after amplifier, and therefore modulate offset and 1/f noise to higher frequencies. Chopping works in continuous time! – Correlated double sampling combines both: first sample signal, then sample inverse, then subtract. Correlated double sampling works in sampled time. CDS can be used most effectively in capacitive sensor systems where the sensor can be controlled to give normal or inverse output signals! Then sensor offset and 1/f noise is reduced too. – In auto-zero and CDS, the transistor bias history must be the same for both samples! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 86 Literature: Switched capacitors [Basu99] S. Basu and G. Temes, "Simplified Clock Voltage Doubler," Electronics Letters, vol. 35, no. 22, pp. 1901–1902, Oct 1999. [Duisters98] Tonny A. F. Duisters and Eise Carel Dijkmans, "A −90-dB THD rail-to-rail input opamp using a new local charge pump in CMOS," IEEE J. Solid-State Circuits, vol. 33, no. 7, pp. 947–955, Jul. 1998. [Enz96] Christian Enz and Gabor Temes, "Circuit Techniques for Reducing the Effects of Op-Amp Imperfections: Autozeroing, Correlated Double Sampling, and Chopper Stabilization," Proc. IEEE, vol. 84, no. 11, pp. 1584–1614, Nov 1996. [Gregorian86] Roubik Gregorian and Gabor Temes, Analog MOS Integrated Circuits for Signal Processing, John Wiley & Sons 1986. [Johns97] David Johns and Ken Martin, Analog Integrated Circuit Design, John Wiley & Sons 1997. [Keshner82] Marvin Keshner, "1/f Noise," Proc. IEEE, vol. 70, no. 3, pp. 212–218, March 1982. [Klumperink00] Eric Klumperink et. al., "Reducing MOSFET 1/f Noise and Power Consumption by Switched Biasing," IEEE J. Solid-State Circuits, vol. 35, no. 7, pp. 994–1001, Jul. 2000. [Schmid02] Hanspeter Schmid, "An 8.25-MHz 7th-Order Bessel Filter Built with Single-Amplifier Biquadratic MOSFET C Filters", Analog Integrated Circuits and Signal Processing, NORCHIP special issue, vol. 30, no. 1, pp. 69–81, January 2002. [Schmid07] Hanspeter Schmid , "Aaargh! I Just Loooove Flicker Noise," IEEE Circuits and Systems Magazine, pp. 32–35, First Quarter 2007. [Schmid08] Hanspeter Schmid, "Offset, flicker noise, and ways to deal with them": Chapter in Circuits at the Nanoscale, CRC Press, 2008, edited by Krzysztof Iniewski. [Wel07] Arnoud P. van der Wel et. al., "Low-Frequency Noise Phenomena in Switched MOSFETs," IEEE J. Solid-State Circuits, vol. 42, no. 3, pp. 540–550, March 2007. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 87 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 88 Feedback or no feedback – The benefit of feedback – Current mode and voltage mode – Example: Open-Loop SigmaDelta A/D converter – Case study with CSEM Zürich: Low-feedback approach applied to buffer design Image from [Black34] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 89 Feedback (in Black's words) Advantages: constancy of amplification freedom from nonlinearity reduced delay and delay distortion, reduced noise disturbance from the power supply circuits Disadvantages: [difficult] because of the [] special control required of phase shifts Unless these relations are maintained, singing will occur © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 90 No free lunch! The famous no-free-lunch theorem states that even if we say, e.g., "A system with feedback gives us low distortion for free", it is not really for free, we just cannot possibly optimize power by trading in distortion or other parameters. A more scientific version of the no-free-lunch theorem states: A general-purpose optimization strategy is impossible, and the only way one strategy can outperform another is if it is specialized to the structure of the specific problem under consideration. from [Ho01] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 91 High-Impedance node in AD844 current-feedback amplifier © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 92 Simple example: voltage-controlled current source © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 93 AD844: the first stage is a Current Conveyor (CCII) © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 94 Current Amplifier without high-impedance node from [Schmid00] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 95 Real difference from [Schmid03] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 96 Very simple, very fast voltage integrator from [Nauta92] © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 97 Impedance mismatch – to decouple – feedback couples again – no FB – – – – – decoupled optimization is much faster optimization space becomes tidier the child finds out more in a shorter time the fool won't fall – Example – aggressive design time – first time right © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 98 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 99 Case Study: Low-feedback approach applied to buffer design Hanspeter Schmid, IME/FHNW Simon Neukom and Yue-Li Schrag, CSEM Zürich © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 100 Standard SC amplifier © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 101 Why an open-loop solution? We needed – Voltage level shift from arbitrary low voltage to 1.6V – Less supply current variation (lowered by 20dB) – 12-bit precise settling at 4 MHz sample rate, 12-bit precise offset Our open-loop continuous-time solution gave – less offset (3σ=3.3mV compared to SC amp's 3σ=11.4mV) – less power (14mW compared to SC amp's 63.5mW) Disadvantages are: – more harmonic distortion – more noise but since this is an output driver after high-gain pre-amplifier chain, both disadvantages do not matter in our application. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 102 Operation principle: (with matched resistors) Stage 1: single-ended voltage to differential current Stage 2: current to voltage © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 103 Offset compensation with current-output Track&Hold Signal is processed in "Hold" mode © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 104 Offset compensation with current-output Track&Hold Offset is compensated in "Track" mode individually for each output path © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 105 The remaining offset comes only from the T&H OTA! All other offsets, including random offsets in the gnd references, are cancelled. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 106 Input transconductor © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 107 Output transresistance amplifier © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 108 Track&Hold amplifier © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 109 Static offset: value settled at the end of calibration cycle Dynamic offset: mean value of full-scale settled values Static Offset Durch Bild oder Grafik ersetzen (Grösse und Position beibehalten) Dynamic Offset © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 110 Static and dynamic offset correlate very well Offsets of two channels do not correlate well digital correction possible! © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 111 Supply current for full-scale steps The current peaks are much smaller than for SC amplifiers © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 112 Monte-Carlo simulation of third-order (left) and second-order (right) harmonic distortion (full scale, full speed) Efficient Simulation of Harmonic Distortion in Discrete-Time Circuits Wednesday May 27, 2009 from 15:30 - 17:00 in Room 101B. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 113 What causes non-idealities? odd-order distortion even-order distortion gain error NOISE © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland offset ISCAS 2009 114 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 115 Design time! – two weeks including all simulations and layout – has been used on three chips – first time right; meets specs © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 116 Literature: Feedback or no feedback [Black34] Harold S. Black, "Stabilized Feed-Back Amplifiers," Electrical Engineering, vol. 53, no. 1, pp. 114–120, Jan 1934. Reprinted in Proc. IEEE, vol. 87, no. 2, pp. 379–385, Feb 1999. [Ho01] Y-C. Ho, D. Pepyne, "Simple Explanation of the No Free Lunch Theorem of Optimization", Proc. 40th IEEE Conf. on Decision and Control, Orlando, pp. 4409–4414, Dec. 2001. [Mahattanakul98] Jirayuth Mahattanakul, "Current-Mode Versus Voltage-Mode Gm-C Biquad Filters: What the Theory Says," IEEE Trans. CAS–I, vol. 45, no. 2, pp. 173–186, Feb 1998. [Nauta92] Bram Nauta, "A CMOS Transconductance-C Filter Technique for Very High Frequencies," IEEE J. Solid-State Circ., vol. 27, no. 2., pp. 142–153, Feb 1992. [Schmid00] Hanspeter Schmid, "Approximating the Universal Active Element." IEEE Trans. CAS–I, vol. 47, no. 11, pp. 1160–1169, Nov 2000. [Schmid03] Hanspeter Schmid, "Why 'Current Mode' Does Not Guarantee Good Performance," Analog Integrated Circuits and Signal Processing, vol. 35, no. 1, pp. 79–90, April 2003. © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 117 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 118 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 119 © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 120 Thank you for coming! Hanspeter Schmid Institute of Microelectronics Steinackerstrasse 1 5210 Windisch Switzerland Tel +41 56 462 46 25 Fax +41 56 462 46 15 hanspeter.schmid@fhnw.ch Lab: http://www.fhnw.ch/technik/ime/ Publications: http://www.schmid-werren.ch/hanspeter/ © Hanspeter Schmid, Institute of Microelectronics, FHNW, Windisch, Switzerland ISCAS 2009 121