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Two Stage CMOS Operational Amplifier: Analysis and Design
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DOI: 10.2139/ssrn.3433181
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Mody University International Journal of Computing and Engineering Research
3 (1), 2019, 40-44
http://www.publishingindia.com/micer
Two Stage CMOS Operational Amplifier:
Analysis and Design
Two Stage CMOS Operational Amplifier: Analysis and Design
Shruti Amplifier:
Suman
Two Stage CMOS Operational
Analysis and Design
Shruti Suman
Department of Electronics and Communication
Engineering, Koneru Lakshmaiah Education
Department
of
Electronics
and
Communication,
Shruti Suman
Foundation (Formerly:
K
L
University),
Guntur,
Andhra
Pradesh, India.
Engineering,
Koneru
Lakshmaiah
Education
Department
ofshrutisuman23@gmail.com
Electronics and Communication,
Email:
Foundation,Koneru
Guntur,Lakshmaiah
Andhra Pradesh,
India.
Engineering,
Education
Email: shrutisuman23@gmail.com
Foundation, Guntur, Andhra Pradesh, India.
Email: shrutisuman23@gmail.com
Abstract:
This
paper describes
analysis
design of 2-stage
operational
(Op A
Amp).
The
Abstract:
This paper
describes
analysis and
designand
of 2-stage
II. TCMOS
wo Stage
CMOS amplifier
Operational
mplifier
designed
circuit
operates
at
3.3
V
of
supply
voltage
and
at
tsmc
0.35
μm
CMOS
technology.
The
performance
CMOS
operational
amplifier
(Op
Amp).
The
designed
circuit
Abstract: This paper describes analysis and design of 2-stage CMOS operational amplifier (Op Amp). The
parameters
such
as:gain,
phase
margin,
GBW,
ICMR,
Slew
Rate,
Offset,
CMRR,
output
etc. alsoof
have
operates
at 3.3 Vcircuit
of supply
voltageatand
0.35 μm
CMOS
Op
Amps
are
most
important
spine swing
for
analog
designed
operates
3.3atVtsmc
of supply
voltage
and at
tsmc
0.35
μm
CMOS
technology.
Thedesigning
performance
been The
analyzed
simulation
whichsuch
isGBW,
carried
out using
Cadence
Virtuoso
Tool.
TheonOp-Amp
is designed
to DC
technology.
performance
parameters
as: ICMR,
gain,
circuit,
andOffset,
performance
relies
data transmission
and
parameters
suchafter
as:gain,
phase margin,
Slew
Rate,
CMRR,
output
swing
etc.
also have
display
aGBW,
unity
gain
frequency
of 7.85
andout
exhibits
a gain
of Virtuoso
86.23 dB Tool.
with
aThe
49°Op-Amp
phase
Obtained
phase been
margin,
ICMR,
Slew Rate,
Offset,
CMRR,
The
symbolic
representation
of margin.
a 2is stage
Op to
Amp is
analyzed
after
simulation
which
is MHz
carried
usinggain.
Cadence
designed
resultsaetc.
also
agree
with
theoretical
predictions.
outputdisplay
swing
also
have
been
analyzed
after
unity
gain
frequency
of 7.85
MHzsimulation
and exhibits arevealed
gain of by
86.23
dBFig.
with
using
1. a 49° phase margin. Obtained
alsoout
agree
with
theoretical
predictions.
whichresults
is carried
using
Cadence
Virtuoso
Tool. The OpPrincipal part of Op Amp is differential amplifier which has two
Scaling
anda differential
amplifier, of
Stability,
Amp isKeywords:
designed to
display
unity gain frequency
7.85 Two stage operational amplifier.
inputs i.e. upsetting and non-reversing voltages which results in
MHzKeywords:
and exhibitsScaling
a gain of
86.23
dB with aamplifier,
49° phaseStability,
margin. Two stage operational amplifier.
and
differential
yielding of differential voltage or current [12].
Obtained results
also
agree with theoretical predictions.
I.
INTRODUCTIO
N
I. Scaling
INTRODUCTIO
Keywords:
and differential amplifier, Stability, Two
N
stage operational
amplifier.
The operational
amplifier (Op Amp) is surely one of the
maximum
beneficial
gadgets
in electronic
industry
The operational amplifier
(Op Amp)
is surely
one of[1-4].
the
OpAmps
are
most
useful
electronic
devices
these[1-4].
days,
maximum beneficial
gadgets in electronic industry
I. Introduction
used drastically
signalelectronic
conditioning,
filtering
OpAmps
are mostfor
useful
devices
these and
days,for
execution
of
mathematical
operations
[5-7].
Op
Amp
used
drastically
for
signal
conditioning,
filtering
and
for is
The operational amplifier (Op Amp) is surely one of the
basically
differential
amplifier
and
output
signal
execution
of
mathematical
operations
[5-7].
Op
Amp
isis
maximum beneficial gadgets in electronic industry [1-4].
nothing differential
however difference
ofand
the output
two input
signals
basically
amplifier
signal
is
Op Amps are most useful electronic devices these days, used
implemented
at difference
the excessive
terminals
nothing
of theimpedance
twoforinput
signals
drastically
for however
signal conditioning,
filtering
and
execution
of
magnified
by
using
a
steady
benefit
[8].
implemented
at
the
excessive
impedance
terminals
Fig. 1: Symbolic Diagram of a Two Stage Op Amp
mathematical operations [5-7]. Op Amp is basically differential
Fig. 1: Symbolic Diagram of a Two Stage Op Amp
The design
of Op
Ampsbenefit
basically
supply
magnified
by using
a steady
[8]. considers,
amplifier
and
output
signal
is
nothing
however
difference
of
Fig.
1: Symbolic Diagram of a Two Stage Op Amp
voltage
and
channel
lengths
of
transistor
with
era
of
Theinput
design
of implemented
Op Amps basically
considers,
supply
the two
signals
at
the
excessive
impedance
CMOSand
technology
with
tradeoff
among velocity,
energy,
voltage
channel
lengths
ofbenefit
transistor
era
of
terminals
by using
steady
[8]. with
gainmagnified
and
some
otheratradeoff
parameters
which
signifies
CMOS
technology
with
among
velocity,
energy,the
performance
[9-10].
The gain
design
of Op
Amps
basically
considers,
voltage
and
some
other
parameters
whichsupply
signifies
the
Nowadays
high
gain in
Amp
is technology
for various
performance
[9-10].
and channel
lengths
of transistor
withOp
era of
CMOS
applications
also
optimizing
has
high
gain
inenergy,
Op various
Amp
isparameters
for
with Nowadays
tradeoff
among
velocity,
gain and
somevarious
other
become
mandatory,
which
results
in
increase
in
slew
rate
applications
also optimizing
various[9-10].
parameters has
parameters
which signifies
the performance
for increase
in current
[11].
become
mandatory,
which
results in increase in slew rate
Nowadays
high gain
inremaining
Op Amp
for of
various
applications
also
the paper
includes
few
forFramework
increase
inof
current
[11]. ispart
optimizing
various
parameters
has
become
mandatory,
which
sections:
Section
II
of
this
work
talks
about
the
two-stage
Framework of remaining part of the paper includes few
amplifier
design
III for
segment
audits
thethe
2 stage
CMOS
results
in increase
in slew
increase
in
current
[11].
sections:
Section
IIand
ofrate
this
work
talks
about
two-stage
Op Ampdesign
schematic
plan,
specifications
and
discussion
on
amplifier
and
III
segment
audits
the
2
stage
CMOS
Framework
of remaining
part of the
includes
fewbeen
sections:
calculation
of formula
for paper
designing
have
done.
Op
Amp
schematic
plan,
specifications
and
discussion
on
SectionArea
II ofIV
thisexhibits
work talks
about
the two-stage
amplifier
the
simulation
results,
supported
calculation
of formula
forthe
designing
have
been
done.
design
and
III
segment
audits
2
stage
CMOS
Op
Amp
bygraphs
and
tables
for
advanced
methodology.
V section
Area IV exhibits the simulation results, supported
schematic
plan,
specifications
and
discussion
on
calculation
includesand
scaling
and lastmethodology.
section finishes
up the
bygraphs
tableseffects
for advanced
V section
of formula
for
designing
have been done. Area IV exhibits the
work
with
conclusion.
includes scaling effects and last section finishes up the
simulation results, supported bygraphs and tables for advanced
Fig. 2: Stage CMOS Op-Amp
work with
II. Vconclusion.
TWO
STAGE
CMOS
OPERATIONAL
methodology.
section
includes
scaling
effects and
last section
Fig. 2: Stage CMOS Op-Amp
The following Fig.
block
is used
to change
the differential
2: Stage
CMOS
Op Amp
MPLIFIER
finishes up
with
conclusion.
II.the work
TA
WO
STAGE CMOS OPERATIONAL
sign
produced
by
the
main
square
into
a
solitary
finished
Op Amps A
areMPLIFIER
most important spine for designing of The following block is used to change the differential
adaptation
[12].
Much
of
the
time
the
increase
given
analog
performance
on data
sign produced by the main square into a solitary finishedby
Op
Amps circuit,
are mostand
important
spine forrelies
designing
of
the information
adequate
transmission
and
DC
gain.
The
symbolic
representation
of
adaptation
[12]. Muchstages
of the isn't
time the
increase and
given extra
by
Article can berelies
accessed
analog circuit, and performance
on online
data at http://www.publishingindia.com
enhancement
is stages
required
which
is produced
a
2
stage
Op-Amp
is
revealed
by
using
Fig.
1.
the
information
isn't
adequate
and
extraby
transmission and DC gain. The symbolic representation of
intermediate stage
[13].
part of isOp
Amp isbydifferential
which enhancement
is required
which is produced by
a Principal
2 stage Op-Amp
revealed
using Fig. amplifier
1.
has
two
inputs
i.e.
upsetting
and
non-reversing
voltages
intermediate
stage
[13].
Principal part of Op Amp is differential amplifier which
III.
WORKING OF THE CIRCUIT
of differential
voltage voltages
or current
which
has
two results
inputs in
i.e.yielding
upsetting
and non-reversing
III.
WORKING OF THE CIRCUIT
[12].
Two Stage CMOS Operational Amplifier: Analysis and Design 41
The following block is used to change the differential sign
produced by the main square into a solitary finished adaptation
[12]. Much of the time the increase given by the information
stages isn’t adequate and extra enhancement is required which
is produced by intermediate stage [13].
Output pole,
P2 =
- g m6
CL
(5)
Z1 =
g m6
Cc
(6)
RHP zero,
III. Working of the Circuit
Fig. 2 is equivalent to typical CMOS Op Amp, includes three
subsections: differential gain stage with next gain stage and
bias stage [14].
CMR (Positive),
1
Ê I5ˆ 2
=
V in(max) V DD Á ˜ - ÍÎV T 03˙˚ (max) + V T 1(min)
Ë b 3¯
The primary phase of Op Amp is differential amplifier made
up with transistors M1, M2, M3, and M4. This is basically a
current mirror (CM) with active type of load utilized here has
Fig. 2 is equivalent
three particular preferences
[15]. to typical CMOS Op Amp, includesCMR (-Ve),
three subsections: differential gain stage with next gain
The second stage stage
used and
to deliver
high
bias stage
[14].gain to the amplifier and
made up with of transistors M5 and M6.
V
in (max)
 V DD
 I5 


 
 3
(7)
(7)
1
2

V T 03
(max)
 V T 1(min)
1
Ê ˆ2
CMR
(-Ve),= V + I 5
V in(min)
SS Á
˜ + V T 1(max) + V DS 5( sat )
Ë b 1¯
The primary phase of Op Amp is differential amplifier
made
up with
transistors M1,
M2, M3, and M4.
This is
The biasing circuit
stage
of amplifier
is accomplished
with
basically a current mirror (CM) with active type of load
transistors M5, M6,
M7, and M8.
utilized here has three particular preferences [15].
 I5 
Voltage
 
 V   condition),
V (Saturation
The second stage used to deliver high gain to the
  V
1


amplifier
made upCMOS
with of transistors
Design Methodology
forand
2-Stage
Op AmpM5 and M6.
(8)
1
2
in (min)
The biasing circuit stage of amplifier is accomplished
transistors M5,
M7, andthe
M8.amplifier:
Following are the with
specifications
for M6,
designing
 V DS 5 ( sat )
T 1(max)
SS
Ê 2 I DS ˆ
Voltage (Saturation condition),
V DS ( sat ) = Á
Ë b ˜¯
Process = 0.35 μmDesign Methodology for 2-Stage CMOS Op Amp
Leff = 1.4 μm
Following are the specifications for designing the
amplifier:
VDD = 3.3 V
Process = 0.35 μm
VSS = 0 V
Leff = 1.4 μm
Slew Rate = 10 V/μsec
VDD = 3.3 V
Product of gain and
bandwidth
(GB) = 10 MHz
VSS
=0V
(8)
V
DS
 2I DS 
  


( sat )  
1
2
1
2
(9)
(9)
Slew Rate = 10 V/μsec
Load capacitance Product
= 2 pF of gain and bandwidth (GB) = 10 MHZ.
= 2 pF
ICMR + Vin (max) =Load
2.7 capacitance
V
ICMR+ Vin(max) = 2.7 V
ICMR – Vin (min) =ICMR-)V
0.4 V in(min) = 0.4 V
Equations used for designing:
Equations used forSlew
designing:
rate,
Slew rate,
SR 
I
C
(1)
5
C
I5
Gain for 1st stage,
SR =
(1)
Cc
A
Gain for 1st stage,
V1

g
g
ds 2
g m 2gain,
AVSecond-stage
1 =
g ds 2 + g ds 4
Second-stage gain,
Fig. 3: Schematic of 2-Stage OpAmp
ds 4
(2)
AV 2 
g
g m6
AVGain-bandwidth,
2 =
g ds 6 + g ds 7
Gain-bandwidth,
(2)
m2
g
g
ds6
(3)
m6
g
ds7
(3)
GB 
gm2
GB =
Output
pole,
Cc
g
C
m2
(4)
C
2

g
C
m6
(5)
L
RHP zero,
g
AC Analysis
IV.phase
Simulation
Outcomes
For this, gain and
margin analysed
with initial
frequency 1 Hz and stopping Frequency 10 MHz.
AC Analysis
Results of AC analysis are:
For this, gain
and phase
analysed
with=7.85
initial frequency
Product
of gain margin
and bandwidth
(GBW)
1 Hz and stopping
Frequency
10
MHz.
MHz

(4)
P
Fig. 3: Schematic of 2-Stage Op Amp
IV.
SIMULATION OUTCOMES
(6)
Phase margin = 49°
Resultsof AC
are:
Gainanalysis
= 86.23 dB
 3dBof
frequency
= 410
Hz
∑∑ Product
gain and
bandwidth
(GBW) = 7.85 MHz

CMRR = 93 dB
42 Mody University International Journal of Computing and Engineering Research
Volume 3, Issue 1, 2019
∑∑ Phase margin = 49°
DC Analysis
∑∑ Gain = 86.23 dB
By the DC analysis we calculate ICMR range and input-output
offset voltage. For this sweep the DC voltage from 0 to 3.3 Volt.
The obtained offset and ICMR range are:
∑∑ 3 dB frequency = 410 Hz
∑∑ CMRR = 93 dB
∑∑ Input offset = 5 μV
∑∑ Output offset = 0.1 mV
∑∑ ICMR range = 0.19 V - 3.1 V
Fig. 7: Analysis of Slew Rate
Fig. 4: AC Analysis
Fig. 4: AC Analysis
Fig. 4: AC Analysis
Fig. 4: AC Analysis
Fig. 4: AC Analysis
Fig. 7: Analysis of Slew Rate
Fig. 7: Analysis of Slew Rate
TABLE I: COMPARISON
IN E XITING
STAGE CMOS
OP AMPAND MODIFIED TWO
TABLE I: COMPARISON IN E XITING AND MODIFIED TWO
TABLE
I: COMPARISON
IN
E XITING
M
ODIFIED
TWO
STAGE CMOS
OP AAND
MP of
Fig.
7: Analysis
Slew Rate
Parameters
Existing
Modified
Fig. 7: Analysis of Slew Rate
STAGE CMOS
AMP 3.3Modified
Power supply
5Existing
VOPIN
V MODIFIED TWO
Parameters
TABLE I: COMPARISON
E XITING AND
Parameters
Load
capacitance
Power
supply (CL)
10Existing
pF
2 Modified
pF
5inVE
STAGE
CMOS
P A3.3
MP
Table I: Comparison
xitingOand
MV
odified Two Stage
Gain
77.249
dB
86.23
dB
Power
supply Parameters
5 pF
V
3.3
CMOS
O
p
A
mp
Load capacitance
(CL)
10
2
pF
Existing V Modified
Phase
53.46°
49°
Load
capacitance
(CL)
10 pFdB 5 V
2 pFdB 3.3 V
Gainmargin
77.249
86.23
Power supply
Parameters
Existing
Modified
GBW
8.6
MHz
7.85
MHz
Gain
dB 10 pF86.23
Phase margin
53.46°
49° dB 2 pF
Load capacitance77.249
(C
L)
Power supply
5 410
V Hz
3.3 V
3Phase
dB freq.
1.3 KHz
margin
53.46°
49°
GBW
8.6
MHz 77.249
7.85
MHz 86.23 dB
Gain
dB
Load capacitance (CL)
10 pF
2 pF
W1=W2
12
4.2
GBW
8.6 KHz
MHz 53.46°
3 dB freq.
410 MHz
Hz 86.23
49° dB
GainPhase margin 1.3
77.249 7.85
dB
W3=W4
23
2.8
3W1=W2
dB freq.
1.3
KHz
410
Hz
12
GBW
8.6 MHz4.2
7.8549°
MHz
Phase
margin
53.46°
W5=W8
20
14
Fig. 5: Waveforms of Transient Analysis
W1=W2
12 8.6
4.2 7.85
W3=W4
23
GBW
3 dB freq.
1.3MHz
KHz2.8
410 MHz
Hz
W6
195
19.4
3 dBW1=W2
freq.
410
W3=W4
23 1.3 KHz
2.8
W5=W8
20
12 14
4.2Hz
Fig. 5: Waveforms of Transient Analysis
W7
90
55
Fig. 5: Waveforms of Transient Analysis
W1
=
W2
12
4.2
W6
195
W5=W8
20
14
W3=W4
23 19.4
2.8
Fig. 5: Waveforms of Transient Analysis
Input offset
6 mV
5 μV
W4
23
2.8
W7 W3 =W5=W8
90
55
20 19.4
14
W6
195
Fig. 5: Waveforms of Transient Analysis Output offset
10 mV
0.1 mV
W5 = W8
20
14
195 5 55
19.4
Input offsetW6
6 mV
μV
W7
90
Positive slew rate
10.4 V/μsec
10.6 V/μsec
W6
195
19.4
W7
90 0.1
55
Outputoffset
offset
10
mV
Input
6 mV
5 μV
Negative
slew rate
9.4 V/μsec
9.7
W7
90 V/μsec
55
Input
6 mV
Positive
slew
rateoffset 0.9-3.27
10.4
10.6
Output
offset
10V/μsec
mV
0.1V/μsec
ICMR
range
V
0.19-3.1
VmV 5 μV
Input offset
6 mV
5 μV
Output
mV
mV
Negativeslew
slew
rateoffset 80.895
9.4 V/μsec
9.7
Positive
rate
10.4
V/μsec1010mV
10.6
V/μsec0.1
CMRR
dB
93
dBV/μsec
Output
offset
0.1 mV
Positive
V/μsec
ICMRdissipation
range
0.9-3.27
V10.4240
0.19-3.1
V10.6 V/μsec
Negative
slew
rate slew rate
9.4µW
V/μsec
9.7
Power
480
µWV/μsec
Fig. 6: Output for ICMR
DC Analysis
Fig. 6: Output for ICMR
Positive slew rate
10.4 V/μsec
10.6 V/μsec
Negative
slew
rate
9.4
V/μsec
9.7 V/μsec
CMRRNegative
80.895
93
Settling
time
µs dB
0.42
µs dB V
ICMR
range
0.9-3.27
V V/μsec
0.19-3.1
slew rate 0.4
9.4
9.7
V/μsec
ICMR
range
0.9-3.27
V
0.19-3.1
Powerswing
dissipation
480
240
Output
V µW
0-3.13
ICMR
range 0-3.28
0.9-3.27
V93VµW
CMRR
80.895
dB
dB 0.19-3.1VV
CMRR
80.895dB
dB µW
CMRR
93 dB
dB
Settling
time
0.4 µs
0.42
µs 93
Power
dissipation
480
µW80.895
240
Power
dissipation
480
µW
240
µW
Power
dissipation
480
µW
240
µW
Output swing
0-3.28
0-3.13
V
Settling
time
0.4Vµs
0.42 µs
Settling
timetime
0.4
0.42
µs
Settling
0.4µs
µs
0.42 µs
Output swing
0-3.28 V
0-3.13 V
Output
swing
0-3.28VV
0-3.13
Output
swing
0-3.28
0-3.13 VV
By the DC analysis we calculate ICMR range and inputoutput offset voltage.
this sweep
the DC voltage from
Output
for ICMR
DC
Analysis Fig. 6: For
0 to 3.3 Volt. The
obtained
offsetfor
ICMR range are:
Fig.
6: Output
ICMR
Fig. 6:and
Output
for ICMR

Input
offset
=
5
μV
DC
Analysis
By the
DC analysis we calculate ICMR range and inputOutput
offsetFor
= 0.1
DC
Analysis
outputoffset
voltage.
thismV
sweep the DC voltage from
DC
ICMR
0.19
V-3.1
V ICMR
By
analysis
we=calculate
ICMR
range
andare:
input0 tothe
3.3
Volt.
Therange
obtained
offset
and
range
3 inputBy
the
DC
analysis
we
ICMR range
output offset
voltage.
this sweepcalculate
the DC voltage
from and
Input
offset =For
5 μV
output
offset
voltage.
For
this
sweep
the
DC
voltage
from
0 to 3.3
Volt.
The
obtained
offset
and
ICMR
range
are:
 Output offset = 0.1 mV
0 to
3.3 Volt.
The obtained offset and ICMR range are:
 Input
offset
=
5
μV
ICMR range = 0.19 V-3.1 V
 Input
 Output offset
= 0.1offset
mV = 5 μV
3

Output
 ICMR range = 0.19 offset
V-3.1 =V0.1 mV
 ICMR range = 0.19 V-3.1 V
Two Stage CMOS Operational Amplifier: Analysis and Design 43
Reference Width for all transistors is mentioned in Table III.
TABLE III: REFERENCE
WIDTH
ALL TRANSISTORS
Table
III: OF
Reference
Width of All Transistors
Name
Value
W1=W2
4.2
Name
Value
W3=W4
2.8
W5=W8
W114= W2
4.2
W6
19.6
W355= W4
2.8
W7
W5 = W8
TABLE IV: VARIATION IN OP AW6
MP PARAMETERS WITH
VARIATION IN LENGTH
Parameter
Gain
Fig. 8: Result of CMRR
Fig. 8: Result of CMRR
Transient Results and Analysis
GBW
L = 0.35
W7
L = 0.7
L = 1.05
L = 1.4
dB
dB
8.77
7.85
14
19.6
55
Table
IV: V75.32
ariation
Op Amp P
arameters With Variation in
54.31 dB
dB in83.46
86.23
Length
12.39
10 MHz
Parameter
L = 0.35
L = 0.7
L = 1.05
L = 1.4
MHz
MHz
MHz
The negative (inverting) port of amplifier is connected
54.31 dB 75.32 dB 83.46 dB 86.23 dB
with sinusoidal input of 1 mv amplitude with 1 MHz 3 dB freq. Gain
29 KHz
1.85
635 Hz
410 Hz
Transient
Results
and Analysis
frequency
for input-output
waveform.
GBW
12.39
10 MHz
8.77
7.85 MHz
KHz
MHz
MHz
TABLE II: VARIATION IN OP AMP PARAMETERS WITH
The negative (inverting) port of amplifier is connected Phase
with
61°
51°
3 dB
freq. 54° 29 KHz
1.8549°
KHz 635 Hz
410 Hz
VARIATION IN COMPENSATION CAPACITOR
sinusoidal input of 1 mv amplitude with 1 MHz frequency
for
margin
Phase margin
61°
54°
51°
49°
Cc
Phase
Gain
GBW
3 dB freq.
input-output
waveform.
Margin
VI.
CONCLUSION
Table II:1.4p
Variation
in Op Amp Parameters With Variation in
86.23 dB
354 Hz
6.86 MHz
52°
VI.2-stage
Conclusion
The analysis of design specifications for
CMOS
Compensation Capacitor
Op Amp including simulation results has done in this
1.3p
Cc
1.4p
1.3p
1.2p
1.1p
1.0p
51°
86.23 dB
380 Hz
86.23 dB
410 Hz
7.33 MHz
work. The mentioned results and graphs also depicted in
analysis
of design
specifications
the which The
estimates
the limits
of scaling
for several for 2-stage CMOS Op
Phase
Gain
GBW 7.853 MHz
dB freq.applications
Amp
including
simulation
and devices. Designed Op Amp results
has high has done in this work.
1.1p
86.23 dB
448 Hz
8.19 MHz
Margin48°
gain circuit The
for thementioned
application like
comparators.
results and graphs also depicted in the which
1.0p52° 46° 86.23
86.23
dB
493
9 6.86
MHz MHz
dB
354Hz
Hz
estimates the limits of scaling for several applications and
REFERENCES
51°analysis of86.23
dB connect
380
Hz input 7.33
MHz
devices. Designed Op Amp has high gain circuit for the
For the
slew rate
a pulse
to nonP. Allen,application
and D. Holmberg,
CMOS Analog Circuit
like comparators.
inverting
with 1dB
us pulse width
and pulse7.85
period
49° terminal86.23
410 Hz
MHz1. Design,
2nd ed., 1998.
is 2 us. The obtained slew rate (SR) isdB= 10.6 V/μsec
448 Hz
8.19 MHz2. S. Suman, “Design of efficient ring VCO using nano
48°Positive 86.23
slew rate
scale double gate MOSFET,” Mody
University
46°Negative86.23
slew rate
=
9.7
V/μsec
References
dB
493 Hz
9 MHz International Journal of Computing and
Engineering
1.2p

49°
Output swing = 0-3.13 V
Research, vol. 2, no. 1, pp. 5-10, 2018.
 Settling
time =rate
0.42 connect
µs
For the analysis
of slew
a pulse input to 3.nonAllen,
and
D. Holmberg,
S. Suman, [1]
K. G. P.
Sharma,
and P.
K. Ghosh,
“250 MHz CMOS Analog Circuit
inverting terminal
with
1
ms
pulse
width
and
pulse
period
is
multiphase
delay
locked2nd
loop
for
low power
Design,
ed.,
1998.
V.
SCALING AND ITS CONSEQUENCES
applications,” International Journal of Electrical and
2 ms. The obtained slew rate (SR) isS. Suman,
“Design
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Scaling can be characterized by power dissipation,
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December, 2017. nano scale double gate MOSFET,” Mody University
operational
cost, V/μsec
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4. S. Yellampalli, and A. Srivastava, “A comparatoretc. However, there are challenges on production, cost
∑∑ Negative
slew rate = 9.7 V/μsec
Journal
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and mixed-signal
based IDDQ testingInternational
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th
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Research, vol. 2, no. 1, pp. 5-10,
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We assumed
∑∑ Output
swinghere:
= 0-3.13 V
(W/L)nmos
∑∑ Settling time
= 0.42=µsfRef * (W/L)1
(10)
Circuits and Systems, IEEE (2005).
S. Suman,
K. G.
Sharma,
and P. K. Ghosh, “250 MHz
5. Jhon, and[3]
K. Martin,
Analog
Integrated
Circuit
Design, Wiley India
Pvt. Ltd, 1997.
multiphase
delay locked loop for low power applica6. Vaishali, S. Suman, K. G. Sharma, and P. K. Ghosh,
tions,” International
Journal
of Electrical and Computer
“Design of ring oscillator
based VCO with
improved
performance,” Innovative
Systems
Design
Engineering,
vol. 7,
no. 6,and
pp. 3323-3331, December
Reference channel length = 1.4 um
V. Scaling and Its Consequences
Reference Width for all transistors is mentioned in table
III. be characterized by power dissipation, operational
can
Scaling
frequency, cost, transistor numbers and size, etc. However,
there are challenges on production, cost power, interconnect
losses, etc.
2017.
[4]
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Wiley India Pvt. Ltd, 1997.
We assumed here:
(W/L)nmos = fRef * (W/L)1
Reference channel length = 1.4 mm
(10)
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