Electrical Power Quality and Utilisation, Journal Vol. XII, No. 2, 2006 Harmonic Compensation Using the Sliding DFT Algorithm for Three-phase Active Power Filter K. P. SOZAÑSKI, Member, IEEE University of Zielona Góra, Poland Summary: This paper describes the sliding discrete Fourier transform (DFT) algorithm as an alternative for typical DFT used for spectrum analysis and synthesis. As an example a control circuit for a three-phase 75 kVA parallel active power filter (APF) is used. Such filters have been built and tested. Some illustrative, experimental results are also presented in the paper. The control algorithms of the proposed APF are implemented in the fixed-point digital signal processor TMS320C50. The presented control APF algorithm is a good alternative to classical APF control algorithms, because it allows easy selection of control parameters in mains currents: imbalance, reactive power or harmonics contents. In the proposed circuit transient performance of APF is improved using non-causal predictive current compensation. 1. INTRODUCTION Conventionally, passive LC filters and capacitors have been used to eliminate line current harmonics and to increase the power factor. However, in some practical applications, in which the amplitude and the harmonic content of the distortion power can vary randomly, this conventional solution becomes ineffective. To suppress such harmonics, an active powerharmonic-compensation filter should be used. The parallel (shunt) active power filter (APF) permits compensation of the harmonics and asymmetries of the mains currents caused by nonlinear loads. Two versions of harmonic compensation circuit with current-fed active power filter are possible: without feedback (with unity gain) and with feedback. Because of its better stability an APF without feedback was chosen. The three-phase active power filter tests circuit is shown in Fig. 1. The shunt active power filter injects AC power current iC (Fig. 1) to cancel the main AC harmonic content. To suppress power line harmonics, an active power-harmoniccompensation filter can be used. The parallel (shunt) APF permits compensation of the harmonics and asymmetries of the mains currents caused by nonlinear loads. When It is possible to find in the literature many control algorithms for three-phase active power filters, for example in: [3, 4, 6, 10]. The control algorithm presented in this paper offers many advantages to existing ones. In this paper a new control algorithm with non causal harmonics compensation circuit is presented too. Key words: active filter, harmonics, DSP, Power Quality, Power factor correction spectrum analysis is the DFT, using the efficient implementation fast Fourier transform (FFT). Typically, N-point DFT is calculated for every sample of input signal, for example described in [12]. For this kind of task the sliding DFT algorithm is better than ordinary DFT. Such a solution is very simple and efficient, especially in coherent sampling. The z-domain transfer function for the kth bin of the sliding DFT filter is described by equation H SDFT ( z ) = 1 − z−N 1 − e j 2 ð k N z −1 (1) where: N length of the signal block, typically equal to signal period, k number of frequency bin. The single-bin sliding DFT filter structure is shown in Figure 2. The magnitude frequency characteristic of a singlebin sliding filter for N = 10 and k = 1 is shown in Figure 3a. 2. THE CONTROL CIRCUIT The control algorithm is based on a sliding discrete Fourier transform (DFT). The sliding DFT is well described by Jacobsen and Lyons in [1] and its application in a singlephase APF is presented by author in [8, 9]. 2.1. A Short Introduction to Sliding DFT Spectrum analysis of signal in power electronics is an important measuring technique. The usual method for Fig. 1. Three-phase active power filter tests circuit K.P. Sozañski: Harmonic Compensation Using the Sliding DFT Algorithm for Three-phase Active Power Filter # Fig. 2. Block diagram of single-bin sliding filter in Figure 1 and 5a. To model the nonlinear load a thyristor power controller with resistive loads is used. The power circuit consists of a three-phase IGBT power transistor bridge IPM (intelligent power module) connected to the AC mains through inductors: LC1, LC2, LC3. The APF circuit contains a DC energy storage component, two capacitors C1 and C2. The control circuit is realized using the fixed-point digital signal processor TMS320C50. The digital signal processor is synchronized with the mains voltage by a synchronization unit. It consists of: a low-pass filter and phase locked loop circuit (PLL). The active power filter injects the harmonic current iC, into the power network and offers a notable compensation for harmonics and reactive power. The compensating current can be determined by iC1 (t ) = iL1 (t ) − I m1 sin (wt + j1 ) (2) where: I m1 amplitude of first harmonic. In the case when harmonics compensation is ideal the line current iS1(t) consists in only the first harmonics of mains current iS1 (t ) = I m1 sin (wt + j1 ) Fig. 3. Sliding DFT characteristics for N=10 and k=2: a) magnitude, b) z-domain pole/zero location When phase angle between mains voltage u1 and line current iS is equal to zero the reactive power is compensated too. In Figure 5 three versions of the control circuit are shown: for imbalance, reactive power and harmonics compensations (Fig. 5a), for reactive power and harmonics compensations (Fig. 5b), for harmonics compensation (Fig. 5c). A detailed block diagram of the control algorithm for compensating: imbalance, reactive power and harmonics content is depicted in Figure 6. In this diagram the circuit controlling voltage of DC energy storage (C1 and C1) is omitted for simplicity. The sampling periods can be calculated with the formula Tp = Fig. 4. The block diagram of first harmonic detector The passband and stopband of the filter are very poor but they are adequate for coherent sampled signals. Using the single-bin sliding filter (from Fig. 1) it is possible to build a first harmonic detector. The block diagram of such a circuit is depicted in Figure 4. 2.2. Realization of Control Circuit In this research a three-phase parallel active power filter is used. For the laboratory experiments the parallel APF without feedback was used because of its greater stability. A simplified block diagram of the proposed active power compensation circuit with the parallel APF for power of 75 kVA is depicted $ (3) T1 N (4) where: T1 period of the mains voltage, f1 = T11 frequency of the mains voltage, N total number of samples per mains period. The algorithm is performed N times per mains period. For the mains voltage frequency of f1 = 50 Hz and the chosen number of samples N = 256, the sampling periods is equal Tp = 78.125ms and the sampling rate is equal to fp = 12800 samples/s. The signals representing load currents iL1(t), iL2(t), iL3(t) are converted to digital domain by a 14-bit analog-to-digital converter with sampling ratio fp. For the control algorithm a first harmonic detector using sliding DFT is employed. In this solution only one single-bin sliding DFT filter structure for detecting first harmonic of load current is used. The first harmonic spectral component signal of the load current is calculated by the equation: Power Quality and Utilization, Journal Vol. XII, No 2, 2006 m Fig. 5. Three-phase active power filter with control circuits for: a) unbalance, reactive power and harmonics compensations, b) reactive power and harmonics compensations, c) harmonics compensation ( ) ( ) s1 (nTp ) = s1 (n − 1)T p ⋅ e j 2 ð/ N − iL1 (n − N )Tp + iL1 (nTp ) (5) where: iL1(nTp) s1(nTp) s1((n-1)Tp) discrete signal representing first phase load current, discrete signal representing first harmonic complex spectral component of first phase load current, discrete signal representing previous first harmonic complex spectral component of first phase load current. The discrete signal representing the first harmonic signal of a load current with zero phase angle between mains voltage u1(t) and line current iS1(t) can be described by the equation: ( ) ( ih1 (nTp ) = 2 N s1 nTp sin 2 p50nTp + j1 ) (6) Compensating current signal is the result of a difference between the load current signal and the first harmonic reference sinusoidal signal: ( ) ( ) iC1 (nTp ) = iL1 (nTp ) − 2 N s1 nTp sin 2 p50nTp + j2 (7) K.P. Sozañski: Harmonic Compensation Using the Sliding DFT Algorithm for Three-phase Active Power Filter % Fig. 6. Simplified block diagram of active power filter control circuit using sliding DFT for: current unbalance, reactive power and harmonics compensation In the case when current imbalance must be compensated current ic1(nTp) has to be calculated by the formula: iC1 (nTp ) = iL1 (nTp ) − 2 N ( ( ) ( ) ( ) s1 nT p + s2 nT p + s3 nT p ⋅ sin 2 p50nTp + j1 3 ) ⋅ (8) where: s2(nTp), s3(nTp) discrete signal representing first harmonic complex spectral component signal of second and third phase load current. & In the summing block the resultant magnitude of three phase current is calculated. The magnitude is used to modulate the amplitude of each phase first harmonic reference signal. By subtracting these signals with appropriate input signals the output compensating signals iC1(nTp), iC2(nTp), iC3(nTp) are calculated. 3. RESULTS ACHIEVED A prototype of the three-phase active power filter was built and tested in the laboratory. The simplified diagram of the test circuit is depicted in Figures 1 and 5. As the nonlinear load a thyristor power controller RI31 (from METROL) with the resistive load was used. Power Quality and Utilization, Journal Vol. XII, No 2, 2006 Fig. 7. Experimental waveforms of active power filter in steady-state with the resistive load: load current iL1 (blue), compensating current iC1 (green), line current iS1 (red) Fig. 9. Simplified block diagram of harmonics compensation with non-causal control circuit Fig. 8. Harmonic spectrum of line current iS1 of active power filter in steady-state with the resistive load Figure 7 shows the steady-state performance of the active power filter. Depicted are: load current IL1, compensating current IC1, line current IS1. The harmonic spectrum of the line current IS1 is depicted in Figure 8. The results achieved are comparable to results achieved using classical control algorithms. For example, in the same active power filter an instantaneous reactive power control algorithm was implemented, which results are described in: [10, 11]. 4. NON-CAUSAL SOLUTION The APF control current dynamics is dependent on the inverter output time constant, resulting from APF output inductance and resultant impedance of load and mains. When the value of load current changes rapidly, as in current iL in Figure 7, the APF transient response is too slow [13, 14] the line current iS suffers from dynamic distortion. This distortion causes an increase of harmonic content in the line current, which is dependent on a time constant. In the APF shown in Figure 1 the THD ratio is increased by about 10%. The mains loads can be divided into two main categories: predictable loads and noise-like loads. Most loads belong to the first category. For this reason it is possible to predict current values in subsequent periods, after a few periods of observation. In this solution, for predictable loads, it is possible to use a circuit with non-causal current compensation as shown in Figure 9. This compensation is dependent on the inverter output time constant. Current samples iC(nTp) are stored in DSP memory (sample register) and in subsequent periods of mains current are compared with present samples, then if respective sample differences are less than assumed values the non-causal current compensation algorithm is switched on (switch S1 in position 1), sending to the output non-causal samples iC(nTp). Previous current compensation signal samples iC(nTp) are stored in memory, and are sent to present output in advance. In the experimental circuit the advance time TA is about several hundred microseconds. Because the time constant is dependent on the load parameter an adaptive algorithm to calculate advance time is employed. If load current is changed during a mains period the non-causal current predictive algorithm is switched off (switch S1 in position 2), and the algorithm waits for a steady-state and when detected it once again switches on (switch S1 in position 1). Figure 10 shows the experimental waveforms in the same conditions as the classical control algorithm (Fig. 7). All waveforms (Fig. 10) of the active power filter with non-causal predictive current compensation are in steady-state with the resistive load. Depicted are the following waveforms: load currents iL1, compensating currents iC1, line currents iS1. The harmonic spectrum of the line current iS1 for the circuit without compensation is depicted in Figure 11. Using the new control algorithm with predictive harmonic compensation it is possible to decrease the harmonic contents in power line currents from THD=12.5% to THD=4.3%. K.P. Sozañski: Harmonic Compensation Using the Sliding DFT Algorithm for Three-phase Active Power Filter ' Fig. 10. Experimental waveforms of active power filter in steadystate with the resistive load for non-causal control circuit: load current iL1 (blue), compensating current iC1 (green), line current iS1 (red) 5. CONCLUSION The sliding discrete Fourier transform (DFT) algorithm proves to be a good alternative for typical DFT used for signal spectrum analysis and synthesis. The passband and stopband of filter sliding DFT are very poor and are adequate only for coherent sampled signals In this research control circuits for three-phase 75 kVA parallel active power filter (APF) were implemented. The filter has been built and tested in our laboratory. Some illustrative, experimental results have also been presented in the paper. The new control algorithms of the proposed APF are implemented in the floating-point digital signal processor TMS320C50. The control algorithm is easy to implement, especially using floating point digital signal processors. For fixed point digital processors this algorithm is more difficult, particularly for more precise calculation of a complex signal module. Using non-causal predictive current compensation it is possible to decrees harmonics contents for predictable mains loads. The presented control APF algorithm is a good alternative to classical APF control algorithms because it allows easy selection of mains current parameters: imbalance, reactive power or harmonics contents. The sliding discrete Fourier transform (DFT) algorithm is well suited for other applications in power electronics where spectrum analysis is necessary, for example: power spectrum analyzers, energy meters etc. REFERENCES 1. J a c o b s e n E . , L y o n s R . : The sliding DFT. Signal Processing Magazine, IEEE, 2003, 20, 2. 2. S o z a ñ s k i K . 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F u j i t a H . , A k a g i H . : A Practical Approach to Harmonic Compensation in Power Systems. IEEE IAS Annual Meeting Conf. Rec., 1990. 7. S o z a ñ s k i K . , S t r z e l e c k i R . : A filter bank solution for active power filter control algorithms. 34rd Annual IEEE Power Electronics Specialists Conference - PESC 03, Acapulco, Mexico, 2003, pp. 10151019. 8. S o z a ñ s k i K . : Active Power Filter Control Algorithm using the Sliding DFT. Signal Processing 2003 Workshop, Poznañ, 2003, pp. 6973. 9. S o z a ñ s k i K .: Harmonic Compensation Using the Sliding DFT Algorithm. 35rd Annual IEEE Power Electronics Specialists Conference PESC 04, Aachen, Germany, 2004. 10. S o z a ñ s k i K . , S t r z e l e c k i R . , K e m p s k i A .: Digital Control Circuit for Active Power Filter with Modified Instantaneous Reactive Power Control Algorithm. 33rd Annual IEEE Power Electronics Specialists Conference PESC 02, Cairns, Australia, 2002. 11. D ¹ b r o w s k i A . , S o z a ñ s k i K .: Implementation of control circuit for active power filter using digital signal processor ADSP21061. Signal Processing 2000, Politechnika Poznañska, Poznañ, Poland, pp. 6771. 12. P r o a k i s J . , M a n o l a k i s M . : Digital Signal processing, Principles, Algorithms, and Applications. Third Edition, Prentice Hall Inc., Engelwood Cliffs, New Jersey 1996. 13. S o z a ñ s k i K . , K l y t a M . : Control algorithm for active power filter with improved transient performance. 10th European Conference on Power Electronics and Applications, EPE 2003, Toulouse, France, 2003. 14. S o z a ñ s k i K . : Non-causal current predictor for active power filter. Nineteenth Annual IEEE Applied Power Electronics Conference and Exhibition, APEC 2004, Anaheim, USA, 2004. Krzysztof Sozañski (M1997) was born in Czerwieñsk in Poland, on July 25, 1957. In 1981 he was awarded an MSc degree in electrical engineering, specializing in the field of automation and electric metrology, from the Electrical Engineering Department at the Zielona Góra University of Technology, in Zielona Góra, Poland. In 1999 he received his PhD degree in telecommunications from the Institute of Electronics and Telecommunications at Poznañ University of Technology, in Poznañ, Poland. He is an Associate Professor at the Institute of Electrical Engineering, University of Zielona Góra. His current research interests are in digital signal processing, implementation of digital signal processing methods in digital signal processors, power electronics, and active power filters. He is author or coauthor of more then 70 periodical and conference papers and 1 patent. Address: University of Zielona Góra; ul. Podgórna 50, 65-246 Zielona Góra phone: +4868-3282567; fax: +4868-3254615; e-mail: K.Sozanski@iee.uz.zgora.pl;web page: www.uz.zgora.pl\~ksozansk Electrical Power Quality and Utilization, Journal Vol. XII, No 2, 2006