电 工 技 术 学 报
2013 年 9 月
第 28 卷第 9 期
TRANSACTIONS OF CHINA ELECTROTECHNICAL SOCIETY
Vol.28
Sep.
No. 9
2013
A Novel Two-Phase Doubly Salient Permanent Magnet Motor with
High Power Density and Low Cost
Zhou Zhiqing1
（1. South China University of Technology
Yongxin
Abstract
Chi Yongbin 1
Guangzhou
343400
He Jiaying 2
510641
China
2. HEP-Edriving Co. Ltd
China）
A novel two-phase doubly-salient permanent magnet motor with new windings
configuration(TDSPM) is proposed in this paper. The structure of TDSPM is the same to that of wellknown three-phase doubly salient permanent magnet machine(DSPM). But it is different from the latter
in that two adjacent turns in a phase winding span three stator salient poles and only two phases
winding is formed. The physics model of the TDSPM with 1.8kW output power is derived analytically.
On basis of the finite element analysis, the feature of proposed machine is investigated, including airgap flux distribution and flux linkage of per phase winding. Results show that there is less leakage flux
around the idle stator poles for TDSPM than DSPM. Further, the bipolar and asymmetrical flux linkage
for the proposed TDSPM is revealed, which has a steeper slope than that for the DSPM. Hence, it
exhibits the higher flux rate, better torque density, materials and space utilization compared with the
DSPM. Finally, the dynamic analysis is carried out with the derived physical model. It is shown that
there is no zero torque zones, so starting is not a problem for the proposed TDSPM. There still exists
the torque ripple due to the configuration with the doubly salient pole.
Keywords：Doubly-salient permanent magnet motor(DSPM), two-phase electric machine, new
windings configuration, permanent magnet electric machine, switched reluctance motor(SRM)
1
While mainly applying for the small-medium size
Introduction
power, it is essentially necessary that make the motor
The doubly salient permanent magnet motor
simpler and lower cost; In Ref.[12], a two-phase
(DSPM) with the embedded permanent magnet in
DSPM was presented. Further, due to zero torque
stator iron has been gained wide attentions and deep
zone, a single-phase doubly salient permanent magnet
studies in the past due to the advantage of the wide
generator with similar structure is proposed in
speed range, simple and robust mechanical confi-
Ref.[13], which make the DSPM simpler clearly.
guration, and good heat
radiation[1-11] ;
Furthermore,
Again in Ref.[14], another single-phase doubly salient
the DSPM machine possesses the capability for the
permanent magnet machine(SPDSPM) with same
higher power density and efficiency than induction
structure has been presented. The full-pitch winding
machine, and exhibits wide applications in some
configuration was used to further make the motor
fields which are the requirements of small and
structure simpler. The advantage of less copper loss
medium size
power[1,3,4].
for that type of motor is also revealed.
The past study mainly referred to the DSPM with
The detailed analysis for the SDSPM is made in
concentrated winding around the salient pole in stator
Ref.[15~17], which proves the higher utilization of
iron, the concentrated winding haves some advantages
space and less copper consumption[16] when equal
such as simple and short end winding, but there is the
output power is required. Thus higher power density
small flux linkage change which makes the material
(power/volume) can be obtained by extending the
and space utilization
poor[8].
permanent magnet module into stator slot without coil,
and further demonstrates that the multi-phase doubly
Received April 9, 2013; received revised form June 24, 2013.
salient permanent magnet machine with full pitch
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311
winding and more numbers of stator pole than rotor
in segments constitute two stator slots mutually, The
pole is virtually equal to the flux switched permanent
pole pitch between poles in rotor is 45° mechanical
magnet machine (FSPM) with 12/10 poles, in which
degree arc. The stator pole pitch is 30 mechanical
the end winding gets shorter, but more permanent
degree arc. A single turns is embedded into the stator
magnet modules were required
[11, 16, 17] .
slot; A phase consists of four turns (the phase A is
However, for these machines mentioned above,
there exist some drawbacks such as the zero-torque
formed by A1～A4 or the phase B by B1～B4), in
which the adjacent turns constitute a full pitch turns,
zone, the substantial torque ripples and starting
the winding configuration for one phase is shown in
difficulty, which limit its applications when motoring.
Fig.1c; two adjacent turns in a full pitch turns are
In other sides, the switching loss of the driving circuit
separated by 90° mechanical degree, and span three
for this type of motor would also be increased due to
stator salient poles; thus, the two phases are separated
the more numbers of rotor pole than stator pole
[2] .
by one stator pole piece.
Although there exists no zero torque zone for the
multi-phase
full-pitch
winding
doubly
salient
permanent magnet machine with more numbers of
stator pole than rotor pole, more permanent magnet
are
required,
which
clearly
increases
the
manufacturing and controlling cost.
In this paper, a novel two-phase doubly salient
permanent magnet motor with full pitch winding
(TDSPM) is proposed[18] . The key feature is that its
full-pitch winding turns spans three or more stator
salient
poles.
There
is
only
one-phase
turn
accommodated in a stator slot. In order to explain the
operational principles, the two-phase 12/8 pole
TDSPM is used as an example, which is similar to the
well-known three-phase 12/8 poles DSPM machine
with respect to the structure [9]. The prototype motor,
operation principle, flux distribution and power
capability would be investigated, and dynamic
analysis would also be carried out.
2
2.1
Prototype motor and operation principle
Prototype motor
Fig.1b shows the structure of the proposed two-
phase TDSPM with a stator consisting of four equal
stator iron segments with three salient poles and
permanent magnet modules and a saliency-pole rotor
with eight rotor poles; Four permanent magnet
modules are embedded respectively in between four
stator iron segments, and its magnetizing direction for
the adjacent magnet module is opposed along the
circumference, which results in the unipolar flux in
every stator iron segments; three stator salient poles
Fig.1
Prototypes of TDSPM and DSPM
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For comparison, the well-known DSPM with
stator pole S1 and S2 is half aligned with the moving
12/8 poles combination is also shown in fig.1a, which
pole R1 and R2 respectively. The PM flux goes
is reported in previous
paper [10] .
It is interesting from
through the stator pole S1 and S2 into the moving
fig.1 to note that the windings in the TDSPM is less
component pole R1 and R2. The flux linkage for the
than that in DSPM, in which all stator slots are filled
phase B winding is equal to zero due to the equal
with windings (the phase A is formed by the turns
positive and negative flux, and that for the phase A
A1～A4, the phase B by B1～B4, and the phase C by
winding kept in a maximum. At this moment the
C1～C4). Thereby the larger stator volume is required
phase B winding is energized by negative current,
to accommodate the corresponding permanent magnet
which would make the moving component moved the
module inset into the stator core compared with that
7.5° mechanic angle to the left. Thus, the stator pole
for the proposed TDSPM while the output power for
S2 and moving component pole R2 is aligned,
the DSPM and TDSPM is equal.
through which the flux goes into the moving
2.2
component, as shown in Fig.2e. Then, the phase A is
Operation principle
The operation principle of well-know DSPM with
excited with negative current to make the moving
past [1] .
component moved to the left, as shown in Fig.2f,
Due to the 240° electric angle conducting and two
which shows the moving component is in the 37.5°
phases windings excited at any time, the DSPM with
mechanic angle. It could be noted from Fig.2f that the
6/4 pole or 12/8 pole possesses the capacity for higher
flux goes through stator pole S2 and S3 into moving
power density compared to the switched reluctance
component pole R2 and R3, and the S2 and S3 is half
short pitch winding has been studied in the
motor with the same structure
[1,4] .
aligned with the R2 and R3, which is opposite
The operating principle of TDSPM with two
symmetrically to that shown in Fig.2d. Hence, the
phases is illustrated through one stator core segment
flux linkage of the phase A is zero too. The waveform
with unipolar flux (N polar) shown in Fig.2. The
of the change of the flux linkage, inductance and
winding A1 and B1 are denoted as the phase A and B
reluctance torque from the above analysis is shown in
respectively. In Fig.2a, the stator pole S3 is aligned
Fig.3. One possible conduction sequence for the two
with the moving component pole R2 and the flux goes
phase winding is shown too.
out of the S3 and into the R2. In this position, the
inductance of two phases winding is small. The
moving component would be moved the 7.5 mechanic
angle to the left when two phases windings are
excited with positive current, as shown in Fig.2b. The
flux now goes through the S1 and R1, S3 and R2
respectively. For the equal positive and negative flux,
the flux linkage of two-phase windings is equal to
zero. In Fig.2c, the stator pole S1 is aligned with the
rotor pole R1 after the move component has been
moved the 15 mechanic angle to the left, and the
permanent flux goes through the S1 and R1 into
moving component. The inductance of two phases
winding is small. But the flux-linkage polarity for two
phases winding becomes the opposite compared with
Fig.2
Operation principle of the TDSPM
that shown in Fig.2a. In Fig.2d, the moving
In Fig.3, the magnet flux linking phase A and
component is in the 22.5° mechanic angle, and the
phase B windings is denoted by the symbol  pmA and
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313
pmB respectively, and the pulsating current in phaseA and phase-B by the symbol i A and i B , and the
inductance by L A and L B , and the reluctance torque
T rA and T rB , respectively varying with the rotor angle;
From Fig.3, it can be noted that the phase current are
fully energized at all times, which is the another
advantage over the DSPM with discontinuous ampereturns utilization. It can also be seen that the flux for
phase A and phase B does not change in the second
and third one-third period respectively, so both phases
may act as exciting winding in those intervals.
Fig.4
Drive system including electric circuit and
Similarly to the DSPM, the reluctance torque for the
controller unit
proposed TDSPM is also zero during the whole period
due to the periodical change of the reluctance.
3
Derivative of the physics model
The system model can be deduced from the
relationship between the inductance, flux linkage,
current and the end voltage in per phase winding, as
is shown below.
The total flux for the single turn in per phase is
  LI   pm
（1）
The end voltage per phase is
U  RI 
d
dt
（2）
The flux linkage for per phase is
  N
Fig.3
Idealizing waveform of the TDSPM. Illustration of
its operating principle
As shown in Fig.4 is the drive structure for the
TDSPM. Two phases are connected and supplied by
full bridge circuits. The rotor positions and phase
current (IA_sensor, IB_sensor) are the inputs of the
（3）
And get the back-EMF as below:
d pm 
 dL
d
dI
 N
I  L

dt
dt
d
 dt

（4）
Substituting Equ.(4) into Equ.(2), and multiplying by I, then yields
controller_unit, Using these inputs, the logic unit of
the controller_unit commutates the motor phase
currents by sending the gating_signals to the power
devices(s1～s8). Only two position sensors and two
current sensors are required to detect the rotor
position and two-phase current respectively.
UI  RI 2  N
d pm
dL 2
dI
I  NIL  NI

dt
dt
d


2
d pm
1 d LI
1 dL 2
 RI  N
 N
I   NI
 （5
2
dt
2 d
d
2
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2013 年 9 月
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carried out by using the model presented above.
）
 ——The flux of the single turn,  =[A  B]T;
Where
I——The current for two phases, I=[I A IB ]T ;
 pm——The permanent magnet flux;
N——The turn numbers of per phase winding;
U——The voltage for the two-phase windings, U=[U A U B ]T ;
——The flux linkage for two-phase windings,  =[  A  B ]T ;
Furthermore, the control strategy can be studied based
on the above mode.
4
FE analysis with comparing to the
existing DSPM
The finite elemenr method (FEM) is used to
analyze
ngs respectively, R=[R A R B ] T ;
FEDSPM
prototype,
and
further
necessary parameters would also be obtained from the
analysis
R——The resistances for two-phase windi-
the
demonstrate its operation principle. Also, some
[10, 11, 15 ] .
For the same ratio of stator pole numbers to rotor
salient pole number for TDSPM and DSPM, the air-
L——The inductance for the single turn, L=
[L A M AB , M BA L B ]T ;
gap flux distribution should be identical under the noload condition; Thus, the flux distribution of TDSPM
In which
when the armature windings is excited by current is
M AB , MBA ——The mutual inductance between
two phases windings;
between the TDSPM and DSPM. For fair comparison,
L A , L B ——The self inductance for phase A and
phase B respectively.
Equ. (5) can be further interpreted as below
Pin  Pcu  Wf  Tr  Tpm
mainly investigated and the comparison is carried out
the following assumptions are made:
（1）The main dimension for both types of
machines is identical.
(6)
（2）The permanent magnet module for both
types of machines have the same shape and equal
residual flux density(1.08T), so the volume and total
Where
P in ——The input power, P in =UI;
P cu——The copper loss, P cu =RI
2;
magnetic energy used in both types of machines is
identical.
W f ——The field energy stored in the armature turns, W f =0.5N[d (LI 2)/(dt)];
（3）The end leakage flux is negligible, so the
two-dimensional FEA can be used properly.
T r ——The reluctance torque because of the
change of inductance, T r =0.5NI 2 ·
（4）The winding accommodated in the stator
slot is equal. For simplicity, only one phase winding
(dL/(d ));
T pm ——The reactive torque between the armature turns and PM, Tpm=NI2(d pm/
(d )).
The inductance for the per-phase windings
for the TDSPM is excited. Thus, the amount of copper
winding consumed by the TDSPM is half that by the
DSPM.
The parameters for both types of machine are
listed in Tab.1.
changes symmetrically and the total reluctance torque
Fig.5 exhibits the flux distribution at unaligned
is zero during one stroke, although the inductance
and half aligned position respectively for the DSPM
varying with rotor position is not in symmetry within
with PM and current excitation (The phase A and B
one period, as is shown in Fig.3. So the reactive
excited
torque or aligned torque is the dominant component
respectively). There is the very high concentration of
of the output torque and can be used for estimating
magnet flux apparent in the unaligned stator and rotor
the torque capability of TDSPM. Besides, the
poles tip, and the flux in the aligned stator and rotor
parameters in Equ.(5) can be obtained from finite
pole is decreasing. When the corresponding stator and
element analysis(FEA) and digital simulation can be
rotor poles are rotated gradually to the half aligned
simultaneously
with
+5A
and
-5A
第 28 卷第 9 期
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一种新型高能量密度和低成本 两相双 凸极永磁电机
position, the PM flux is also moved toward the
working stator-rotor pole by the EMF resulting from
armature current.
Fig.6
Flux distribution of the TDSPM machine with
current excitation of I_phaseB=5A
The more detailed air-gap flux distribution
Fig.5
Flux distribution of the existing DSPM machine
with exciting current of I_phaseA=5A and I_phaseB=-5A
Fig.6 exhibits the flux distribution at unaligned
and half aligned position respectively for TDSPM
waveform for the above analysis is shown in Fig.7 for
the unaligned and half-aligned position respectively,
which also includes the flux distribution waveform of
air gap for the DSPM with all phases windings
with PM and current excitation (only the phase A is
excited
excited with +5A). It can be clearly seen that the flux
I_phaseC=-5A) to further exhibit the difference under
different exciting conditions. It is clearly notable that
in idle stator pole is less compared with that for
DSPM. In other words, the leakage flux going
through the idle stator pole in the TDSPM is less,
which would increase the output torque.
(i.e.
I_phaseA=5A,
I_phaseB=-5A,
both the air-gap flux distribution for the TDSPM with
phase B excited and the DSPM with all phases excited
are almost the same except that the smaller amplitude
in the phase B position for the DSPM, and the flux
amplitude in the phase B position for the DSPM with
all winding excited among three conditions is smallest;
However, the flux amplitude around the idle pole of
phase C for the DSPM with only two phase excited is
higher obviously, which means that the larger leakage
flux arises around the idle pole of phase C when the
phase A and B are excited with the equal amplitude
and opposite marker current. The air-gap flux
distribution amplitude in the working stator pole for
both machines is almost equal under three conditions,
which is above the order of 1.8T.
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2013 年 9 月
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Fig.8
Waveform of the flux linkage vs. rotor position
under the rated current level exciting
5
Effect of the leakage flux on the
performance
The above analysis is helpful for understanding
the feature of TDSPM, i.e. the less leakage flux in the
idle stator pole. However the leakage flux would have
a great influence on the energy exchange of this type
Fig.7
Waveform of the air-gap flux-density distribution
of machine. From Fig.5～Fig.8, it has been already
clear that the leakage flux going through an unaligned
Fig.8 shows the flux linkage waveform of per-
stator pole is not negligible when only two phases are
phase winding for two types of machines. Obviously,
excited for the well-known DSPM. Again, it has been
the flux linkage for the well-known DSPM is unipolar
well
and that for the proposed TDSPM is bipolar but
electromagnetic system and an electric source is given
asymmetrical, which is different from that for single
by
phase
DSPM [14-16] ,
in which there is a bipolar and
symmetrical flux linkage. Nevertheless, the flux
known
that
energy
change

E  i d
between
an
（7）
linkage waveform for the proposed TDSPM has the
The locus of flux linkage and current in the flux
steeper slope ( 1 ＞  2 ) compared with that for the
well-known DSPM due to the asymmetric structure
linkage-current plane as rotor rotates for one stroke is
around the phase winding. It can also be notable from
converted to mechanical form. For salient pole PM
Fig.8 that the change rate of flux linkage for the
motors, three stages starting to rise, keeping constant,
TDSPM is approximately twice that for the DSPM. In
falling at full aligned would happened in sequence
terms of the Equ.(2) and Equ.(5), the amplitude of
during one stroke. Fig.9 shows the relationship of the
Back-emf for the TDSPM is also approximately twice
current vs flux during one stroke.
that for the DSPM. Hence, the proposed machine
possesses the performance of higher power density.
a closed loop. The area enclosed equals the energy
For the DSPM, the exchange energy when three
phases excited during one stroke corresponds to the
W_dspma, W_dspmb and W_dspmc and that when two
phases excited during one stroke only corresponds to
the W_dspma and W_dspmb, which is shown in Fig. 9.
Hence the W_dspmc is equal to the loss from leakage
flux when two phases are excited only. In Fig.9, for
the TDSPM, the exchange energy when the phase B is
第 28 卷第 9 期
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一种新型高能量密度和低成本 两相双 凸极永磁电机
excited corresponds to the W_TDSPM, which is
of static torque against rotor position. Flux-linkage
almost equal to the sum of W_dspma, W_dspmb and
was determined as a function of current by integrating
W_dspmc; it is deduced from the Fig.8 and Equ.(2)
current waveforms upon imposition of a step voltage
that the back-EMF for the TDSPM is twice that for
waveform
DSPM. In this case, the TDSPM absorbs the electric
measurement was performed using a commercial
power of IE (where the E is equal to the back-EMF
torque transducer, again with the rotor locked. The
with
the
rotor
locked.
The
toque
d  /(dt)), however the DSPM absorbs the electric
static torque measured is shown in Fig.10. There are
power of (3/2)IE. Hence, although the leakage fluxes
major
in the idle stator pole are decreased when three phases
measurement, this mainly is the cause of the leakage
excited for the DSPM, the more leakage flux in the
flux on both ends of the stator cores and the
circumference around the motor would be resulted in,
manufacturing error. Hence, the test validates the
which makes the efficiency degraded.
above analysis.
Fig.9
Flux linkage vs. winding current
errors
Fig.10
between
phases excited for the DSPM, only phase B and two
prediction
and
the
Static torque for the TDSPM and
Fig.10 shows the output torque during one stroke
under different conditions, i.e. two phases and three
the
DSPM machine
6
Analysis of the results
phases excited for the proposed TDSPM respectively.
A 2-phase 12/8-pole TDSPM, as shown in Fig.1,
The torque for the TDSPM with single phase winding
has been designed to illustrate the aforementioned
fed by current is almost equal to that for the DSPM
analysis, For the requirement of operation mode,
with the +5A in the phase A and -5A in the phase B
and C respectively, and much larger than that for the
digital simulation at the low and rated speed has been
only carried out for the design. Both machine data
DSPM with only two phases excited, i.e., the +5A in
and computer results are shown in the. Tab.1 and
the phase A and -5A in the phase C. From the
analysis above, it could be known that the absorbed
Tab.2.
power for the DSPM is more than that for the TDSPM
Tab.1
Machine data
Well-known
Parameter
TDSPM
Stator outer size/mm
160 (Diameter)
160×160
Stator inner diameter/mm
80
80
are fed by current of +5A. It is clear that much higher
Stator pole number
12
12
output torque can be achieved for the proposed
Rotor pole number
8
8
Stator pole arc / ( ° )
15
15
when the equal output torque is required. Further,
there is less copper consumption and higher space
utilization for the TDSPM. Also, Fig.10 includes the
waveform of output torque when two-phase windings
TDSPM, in comparison with the existing DSPM.
The machine has been tested, with measurement
DSPM
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2013 年 9 月
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Rotor pole arc /( ° )
19
19
in Fig.12. The resultant reactive torque T pm is always
Stator slot deep/mm
19
19
greater than zero so that starting is not a problem.
Phase number
2
3
100
100
80×12×32
80×12×32
The turns number of per
phase
Magnet permanent size
(L×W×H) /mm
Tab.2
Performance parameters
TDSPM machine
Parameters
Fig.11
Speed at
Speed at
1 000 r/min
450 r/min
DC bus voltage/V
280
280
RMS voltage/V
236
171
Maximum inductance/mH
35.8
Minimum inductance/mH
-35.7
Phase peak current/A
9
12
Phase RMS current/A
6
7.6
Bus RMS current/A
7.5
6.8
Mean output torque/
(N·m)
Efficiency(%)
Current waveforms for TDSPM at speed
of 1 000r/min
Fig.12
Resultant torque for TDSPM at speed
of 1 000r/min
16.32
20.4
91.92
82.5
At the low speed of 450r/min, the phase current
is almost kept constant, and the current has a
rectangular form, as is shown in Fig.13, the resultant
The computer simulation based on the gone
derived physics model is carried out and these
parameters required are obtained from the FEA. The
current waveforms are shown in Fig.11 at the based
speed of 1 000r/min, the phase current is controlled in
each stroke by chopping and conducted more than 3/5
periods, and the current wave has a trapezoidal form
torque is shown in Fig.14, it is shown that there is
large notched in torque and there also exists a severe
torque ripples for the resultant torque at low and rated
speed due to the current commutation and the
reluctance
torque.
Fortunately,
output
pulsation can be tolerated in some areas of application.
Also, the study on less torque ripples is progressing.
due to the current rise relay; It is possible for the twophases currents to commutate easily within a very
short time due to the minimum inductance position at
this point. From the Fig.3, the no-load torque T no
load
and its ripple is small which almost has little
influence on the overall torque. The reluctance torque
T r is almost near zero, which gives little contributions
to the overall torque. However, reluctance torque
gives rise to the considerable torque ripples, as shown
torque
Fig.13
Current waveforms for TDSPM at
speed of 450r/min
第 28 卷第 9 期
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319
一种新型高能量密度和低成本 两相双 凸极永磁电机
HEP-Edriving Co. Ltd for the financial support.
Special thanks go to He Jiaying for her assistances.
参考文献
[1]
Liao Y, Liang F, Lipo T A. A novel permanent
magnet motor with doubly salient structure[J].
IEEE Trans on TIA, 1995, 31(5):1069-1078.
Fig.14
Resultant torque for TDSPM at
[2]
Cheng
Ming,
Chau
K
T,
Chan
C
C.
Static
characteristics of a new doubly salient permanent
speed of 450 r/min
magnet motor[J]. IEEE Trans on Energy Conversion,
7
Conclusion
2001, 16(1):20-25.
A novel electrical machine with high power
[3]
analysis of 8/6-pole doubly salient permanent magnet
density high efficiency, combined with a mechanical
motor[J]. Electric Machines and Power Systems, 1999,
robust structure and low cost can be realized based on
27: 1055-1067.
the proposed concept in this paper. The main
[4]
advantages of TDSPM are:
Industry Applications, 2003, 39(5): 1363-1371.
[5]
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作者简介 ：Zhou Zhiqing
male, born in 1979. At present, he is
phase doubly salient permanent magnet generator
pursuing the Ph.D. degree. His research interests is in the design of
with
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electronics.Chi Yongbin
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Doctor degree. His research interest is in the mechatronics
male, born in 1946, professor, and tutor for
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一种新型高能量密度和低成本两相双凸极永磁
电机
周智庆
（1. 华南理工大学机械与汽车工程学院
摘要
1
广州
迟永滨
510641
1
何嘉颖
2
2. 江西省荷谱科技有限公司
永新
343400）
提出了一种新型绕组结构两相双凸极永磁电机（TDSPM）。 该新型电机的结构与现
存的三相双凸极永磁电机（DSPM）相同，与后者不同的是，其绕组结构临近线匝跨越三个定子
极，并且只形成两相。分析了该新型电机的工作原理，
以一台 1.8kW 的 TDSPM 电机为例，建
立了其动态物理模型。基于有限元法，调查了该新型电机的特点，包括气隙磁通密度分布以及两
相绕组磁链。进一步结合实验验证，结果显示。与现存的 DSPM 电机相比，TDSPM 的非工作定
子凸极上有更少的漏磁。并且其相磁链具有非对称和双极性的特性，以及更大的变化率，从而，
可以获得更高的反电动势，这使得该新型电机具有更高的功率密度以及绕组和空间利用率。进一
步基于建立的动态物理模型，动态分析被执行，验证了提出的两相 TDSPM 电机不存在零扭矩区
域，在任何位置可以起动。 然而，由于双凸极的结构特征，仍然存在输出扭矩波动的缺陷。
关键词： 双凸极永磁电机
中图分类号： TM351
两相电机
新绕组结构
永磁电机
开关磁阻电机