TUA6045 Half NIM Application Note
TUA6045 Half NIM Application Note
TUA6045 + BF5030W
BG5130R + BB565 + BB659C + BB689
Ver1.0, Released September 2006
Never
stop
thinking.
TUA6045 Half NIM
Overview of the TUA6045 Half NIM
Half NIM with Single Conversion
Tuner
For European DVB-T
application
With Infineon Components :
TUA 6045 Single Chip Mixer-Oscillator PLL IC
with IF Amplifier
BF 5030W and BG5130R self biasing
MOSFETs
BB565, BB659C and BB689 Varactor
Diodes
BAS70-04 Bridge Rectifier
BC847BW BJT Transitor
This very small sized Half NIM consisting of a single conversion tuner designed for DVB-T(COFDM)
front-end in the frequency range from 66 to 858 MHz can be used with minimum modification for all
digital broadcasting reception. The Half NIM was developed for 3 band tuner concept, designed
without switching diodes based on the Infineon 3 band tuner IC. The IC is particularly suitable for
COFDM applications like DVB-T and ISDB-T that requires stringent close-in phase noise. It is also
suitable for ATSC, DAB and MobileTV Application. The IC provides a balanced SAW filter driver
output that is designed to drive a SAW filter directly.
The tuner is optimized for IF bandwidth = 8MHz and IF center frequency = 36MHz.
The frequency ranges of the tuner is as follows :
VHF I : 66 – 154 MHz
VHF II : 162 - 442 MHz
UHF : 450 - 858 MHz
All the passive and active components except air coils, 5 choke coil are SMD components. The PCB
is double-clad and the dimensions are mm.
Semiconductors:
TUA6045 Half NIM
Release September 2006 Ver 1.0
1X
TUA 6045 1 X
BF 5030W
1X
BG 5130R 7 X
BB 565
4X
BB 659C 4 X
BB 689
1X
BAS70-04 1 X
BC847BW
1
TUA6045 Half NIM
CONTENT
1.
Tuner Design .......................................................................................................................
1.1
Circuit Concept
…………………………………………………………………………...
1.2
UHF RF Block
…………………………………………………………………………...
1.3
VHFH RF Block …………………………………………………………………………..
1.4
VHFL RF Block
…………………………………………………………………………...
1.5
Oscillator Resonator, PLL Loop Filter & Phase Noise ………………………………...
1.6
IF Block ……………………………………………………………………………………..
3
3
4
4
4
5
7
2.
PCB
…………………………………………………………………………………………………
8
3.
TUA6045 One Chip RF + IF Amplifier Tuner IC ……………………………………………
3.1
Highlights …………………………………………………………………………………..
3.2
Block Diagram ……………………………………………………………………………...
8
8
9
4.
Alignment
…………………………………………………………………………………………
4.1
Alignment Setup ……………………………………………………………………………
4.2
Alignment Procedure ……………………………………………………………………..
10
10
11
5.
Measurement ………………………………………………………………………………………
5.1
Electrical Characteristics
…...……………………………………………………………
5.2
Frequency Response
..…………………………………………………………………..
5.3
Measurement Results
..…………………………………………………………………..
12
12
13
14
6.
Front End Interface
……………………………………………………………………………..
6.1
Bus Interface
……………………………………………………………………………..
6.2
Tuner PLL Programming ………………………………………………………………….
6.3
Bus Format …………………………………………………………………………………
6.4
Bus Timing …………………………………………………………………………………
6.5
Data Specification, Function and Default ……………………………………………….
19
19
19
21
22
25
7.
Component List and Ordering Information
…………………………………………………..
32
8.
Circuit and Layout
……………………………………………………………………………....
8.1
Schematic and Layout ……………………………………………………………………
8.2
Pinning and Outline Dimension
………………………………………………………....
37
37
40
9.
Automatic Tuner Test Setup of the Team
41
TUA6045 Half NIM
Release September 2006 Ver 1.0
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TUA6045 Half NIM
1. Tuner Design
1.1.
Circuit Concept
The RF input signal is splitted by a simple high pass filter combined with IF & CB(Citizen Band) traps.
Instead of band switching with PIN diodes a very simple triplexer circuit is used. With a high inductive
coupling the antenna impedance is transformed to the tuned input circuits. The pre-selected signal is
then amplified by the high gain self biased MOSFET BF5030W. One BG5130R double-MOSFET can
be used for both VHF bands. In the following tuned bandpass filter stage, the channel is selected and
unwanted signals like adjacent channels and image frequency are rejected. Tracking traps of
prestages and capacitive image frequency compensations of band filters reject especially image
frequencies.
The conversion to IF is done in the one chip tuner-PLL IC, TUA 6045. TUA6045 is a real 3 band
tuner IC which has all the active parts for the 3 mixers, 3 oscillators, an IF driver stage, the complete
PLL functions including 3 PNP ports for the band switching, and a wideband AGC detector for internal
tuner AGC. Combined with the optimized loop filter, 4 bit programmable charge pump currents, the
balanced crystal oscillator, and the voltage controlled oscillators which have superb characteristics
The tuner can achieve distinguished phase noise performance suitable for all digital applications. The
balanced mixer output signal of the TUA6045 is designed to drive directly a SAW filter in the following
IF stage.
The tuner consumes less than 100 mA currents or 0.33 Watt power. This can be a big advantage for
portable or handheld appliances.
BG5130R
Fig 1. Circuit Concept Diagram of DVB-T Tuner
For the detailed circuit description please refer to Appendix A.
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Release September 2006 Ver 1.0
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1.2. UHF RF Block
With the wide range ultra linear varactor diode BB565 it has become possible to design an UHF band
without coupling diodes and without compensating coils for extending the frequency ratio in the tuned
filters. To get a good tracking without a coupling diode between the input filter and the MOSFET the
point of coupling is set between the tuning diode and the series capacitor, and not at the high end of
the resonant circuit.
The bandpass stage is an inductive low end coupling filter, which concurrently provides the
transformation from unbalanced to balanced. Also thanks to the matched image filters on both
prestage and band pass filter stage, better than 65dB image rejection can be achieved over the whole
UHF band. By means of simple gate 1 switching through PNP ports, pre-amplifiers are selected.
1.3. VHFH RF Block
For VHFH band, high quality ratio-extended varactor diode, BB659C is used. To compensate gain,
one additional coupling diode, BB565 is placed on the prestage of VHFH.
The RF bandpass filter is unbalanced on the primary side, and balanced on the secondary side just
like UHF band pass filter. The coupling between filters is realized via a printed inductor. The mixer
input circuit is optimized to protect the mixer from overloading. Image rejection filters work as those of
UHF block.
1.4. VHFL RF Block
For the wide VHFL frequency range a tuning diode with an extended capacitance ratio is required.
BB689 is a tuning diode, which was developed to cover the wide frequency range of Hyperband tuner
and at the same time shows a low series resistance. 2 X BB565 are used for coupling to achieve
improved RF characteristics.
The RF band pass filter is unbalanced, and is also coupled asymmetrically to the high ohmic VHFL
mixer, which has no negative effects due to the relatively low frequencies involved.
After the RF Block circuit design it is preferable to do block simulations to confirm its frequency
dependent characteristics. Fig.2 is one of such simulation results.
Fig 2. One of the Simulation Results of DVB-T Tuner RF Blocks
TUA6045 Half NIM
Release September 2006 Ver 1.0
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1.5. Oscillator Resonator, PLL Loop Filter and Phase Noise
The Oscillator tank circuits were carefully optimized for oscillator range, stability and phase noise. The
layout is also optimized to prevent any kind of unwanted parasitic oscillations, Capacitors of the
resonators could be temperature-compensated if necessary. N750 type is recommended for this
purpose.
One of the most important considerations to design a good DVB-T tuner is how to down-convert input
RF signals to IF frequency with minimized phase noise. The DVB-T standards provides for two modes
of operation, a 2K mode with 1705 subcarriers, and an 8K mode with 6817 subcarriers for
OFDM(Orthogonal Frequency Division Multiplexing) transmission1. An OFDM signal as in Fig.3
contains multiple subcarriers, each of which is a smaller percentage of the total frequency bandwidth
than in a single carrier system. As a result, phase noise is a smaller percentage of the bandwidth in a
single-carrier system. For this reason, phase noise degrades the performance of an OFDM system
more than in a single carrier system.
Fig 3. Typical Spectrum of the simple OFDM signal
Phase noise influences two important system performances : One is receiver selectivity by reciprocal
mixing in Fig.4, and the other is receiver sensitivity or SNR2, which decides BER(Bit-Error-Rate) of the
digital system combined with other noise sources like prestage noise figures, image noise, etc.
Tuner
Output Signals
Input Signals
Local Oscillator
Fig 4. Reciprocal Mixing Model
1
2
. ETSI EN 300 744 V1.2.1
. Muschallik, C., Influence of RF oscillators on an OFDM signal, IEEE Transactions on Consumer Electronics, vol.41,No.3, pp.602603
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To design optimum resonators for the IC, the well-known Leeson's equation3 should always be
reflected. Even though there is an improved phase noise model4 for better phase noise analysis and
prediction, Leeson's equation is still a basis of all those new approaches.
 1  fo  2  fc
 FkT 
 + 1
L( fm) = 10 log  
+ 1

fm  Ps 
 2  2QLfm 





(1)
L(fm) is ratio of noise power in a 1-Hz bandwidth in units of dBc/Hz. fo is the frequency of oscillation.
fc is the flicker noise corner. F is the noise figure of oscillator. Ps is the carrier power. K is
Boltzmann's constant, 1.38x10-23 J/K. T is Kelvin temperature. QLis loaded Q factor.
TUA6045 can satisfy a low intrinsic F requirement of oscillator. The external applications of the
oscillator should be carefully designed not to degrade Q with regard to stable oscillation.
The critical role of loop filter is to remove the reference spurs produced by the phase detection
process, which is fundamentally a sampled system in digital implementations. Since the control
voltage directly modulates the frequency of the VCO, any AC components of tuning voltage results in
a frequency modulation of the oscillator. If these components are periodic, they produce stationary
side-bands like reference spurs. Because of the wide tuning range of the tuner, the tuning sensitivity
of tuner can go up to 35MHz/V, so even a few millivolts of noise on the tuning lines will generate
noticeable spectral interference.
The oscillator's output now has the benefits of phase locking such as improved stability and phase
noise and this is another crucial function of PLL. By determining a proper loop bandwidth, optimum
phase noise characteristics of the reference oscillator and the local oscillator can be utilized. For a
given loop bandwidth, a higher order filter provides more attenuation of out-of-band spectral
components. However, the higher the order, the more poles there are, and it means it gets harder to
make the loop stable. The loop bandwidth and loop filter components should be carefully selected to
achieve optimal phase noise and to reject reference spurs. 4 extended modes of charge pump
currents also must be appropriately chosen and used for best phase noise performance of different
frequency ranges. For this tuner design DVB-T recommended fref=166.667KHz is used for all loop
filter calculations and measurements.
A 3rd order passive loop filer is chosen for the tuner design. The following are simplified procedures to
decide the loop filter components.
1.
2.
3.
4.
Define the basic synthesizer requirements ; oscillator frequency ranges, fref, maximum frequency step,
fBW(Loop
Bandwidth, Hz) with deep consideration of in-out band phase noise.
Identify Kvco(VCO sensitivity, Hz/V) and Icp(charge pump current, A).
Calculate Fstep = fvco_max - fvco_min, to optimize for fvco_max
Calculate N = fvco_max / fref, to optimize for fvco_max.
Calculate natural frequency, Fn ; ζ = damping factor
2 × f BW
Hz
(2)
Fn =
1
2π × (ζ +
)
4 ×ζ
I cp × K vco
6. Calculate C68 ;
Farad
(3)
C 68 =
N × ( 2π × Fn ) 2
7. Calculate R39, and its phase noise contribution. This completes the main part of the loop filter.
5.
R39 = 2 × ζ ×
3
N
I cp × K vco × C 68
ohm
(4)
. G.Vendelin, A.Pavio, U.Rohde, Microwave Circuit Design using Linear & Nonlinear Techniques, John
Wiley & Sons, New York,
1992, pp.385-491.
4
. Hajimiri, A., & Lee, T.H., A genaral theory of phase noise in electrical oscillators, IEEE journal of solid-state circuits, Vol.33, No.2,
pp.179-194.
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Release September 2006 Ver 1.0
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K
2k × T × R39 
 dBc/Hz
LΦ ( fm) = 20 log vco
(5)5

fm


8. Calculate C65, which is used to damp transients from the charge pump and should be at least 20 times
smaller
C 68
than C69, i.e.,
C 69 ≤
20
9. Calculate R40 & C24 within these limits and the phase noise contribution of R40 by Eq.(5).
τ2
τ1=C68×R39,τ2=C24×R40,
0.01 <
< 0.1
τ1
A bigger time constant results in somewhat better filtering action, but tends to be associated with lower
stability.
10. In order to have the confidence in the stability of the loop, an open loop analysis is performed to estimate the
gain and phase margin. By closed loop analysis we can obtain the frequency response & transient response
of
the loop. We use a mathmatic tool to analyse these parameters though a spreadsheet program is enogh for
the
above calculations.
Typically the crystal oscillator used for the reference has very good phase noise that then levels off
near 10KHz offset at around -150dBc/Hz. The free running oscillator to be phase locked typically has
much higher close in noise but continues down to around -120dBc/Hz beyond 1MHz. At some offset
the reference noise multiplied up to the output frequency becomes higher than the oscillator's free
running noise. This is the point where normally the loop bandwidth is set. Inside the loop the oscillator
noise is improved by the reference, yet outside the loop is not degraded by the reference. Because of
the wide tuning range of the tuner oscillator the loop bandwidth should be very carefully chosen with
deep consideration of these noise contribution mechanism.
The phase noise level within the loop bandwidth can be approximated by
Close _ in _ phase _ noise = (1Hz _ normalized _ phase _ noise _ floor) + 20 log N + 10 log f ref
(6)
There are other sources of phase noise that need to be considered when designing the tuner. One of
the most common sources of noise is the power supply to the IC. This can be caused in many ways,
but most commonly are due to supply ripple and electric or magnetic coupling to +3.3V line. Correct
PCB layout and good AC blocking are critical to ensure good noise performance. The highest level
signal line in the tuner is the IF output line, and all those sensitive blocks like oscillator, loop filter and
long DC lines should be well-protected from coupling by IF lines.
1.6. IF Block
TUA6045 has separated mixer outputs and SAW driver inputs to realize an IF filter of band pass filter
structure that helps much better adjacent channel rejection. Especially in simulcasting signal
environment as in Fig.5, it is a big advantage combined with internal AGC of TUA6045 to efficiently
suppress strong adjacent PAL signals. The tuner provides a balanced IF output to drive directly a
SAW filter.
PAL Signal
PAL Signal
DVB-T Signal
Fig 5. Spectrum of a DVB-T signal between strong analog PAL signals
5
. G.Vendelin, A.Pavio, U.Rohde, Microwave Circuit Design using Linear & Nonlinear Techniques, John
Wiley & Sons, New York,
1992, pp.436.
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Release September 2006 Ver 1.0
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TUA6045 Half NIM
2. PCB
Double-sided, 1 mm thickness FR4 PCB is used for the tuner design.
3. TUA 6045, One-Chip RF + IF Amplifier Tuner IC
3.1 Highlights
The core of the tuner is the one-chip mixer oscillator-PLL IC TUA 6045.
The following are some of the outstanding features:
Features
‰
‰
‰
‰
‰
‰
‰
‰
Suitable for DVB-C, DVB-T, ISDB-T and ATSC
Wideband and Narrowband AGC detector for internal tuner AGC
- 5 programmable take-over points
- 2 programmable time constants
Low Phase Noise
Full ESD protection
Mixer/Oscillator
- High impedance mixer input (common emitter) for LOW band
- Low impedance mixer input (common base) for MID band
- Low impedance mixer input (common base) for HIGH band
- 2 pin oscillator for LOW band
- 2 pin oscillator for MID band
- 4 pin oscillator for HIGH band
IF-Amplifier
- IF preamplifier with symmetrical 75Ω output impedance able to
drive a SAW filter
PLL
- 4 independent I2C addresses
- I2C bus protocol compatible with 3.3 V and 5V micro-controllers up
to 400 kHz
- Short lock-in time
- High voltage VCO tuning output
- Internal LOW/MID/HIGH band switch
- Lock-in flag
- 4 bit Programmable reference divider ratio
- 16 Programmable charge pump current
VQFN-48 Package
TUA6045 Half NIM
Release September 2006 Ver 1.0
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TUA6045 Half NIM
3.2 Block diagram
In the block diagram the internal structure of the IC is shown in Fig.6.
Figure 6. Block Diagram of TUA6045, VQFN-48
TUA6045 combines a mixer-oscillator block with a digitally programmable phase locked loop (PLL) for
use in broad-multimedia frontend applications. The mixer-oscillator block includes three balanced
mixers (one mixer with an unbalanced high-impedance input and two mixers with a balanced lowimpedance input), two 2-pin asymmetrical oscillators for the LOW and the MID band, one 4-pin
symmetrical oscillator for the HIGH band, an IF amplifier, a reference voltage, and a band switch.
Mixer outputs and IF SAW Driver inputs are separated to make it possible to realize a band pass IF
filter to suppress adjacent channels efficiently.
The PLL block with four independently selectable chip addresses forms a digitally programmable
phase locked loop. With a 4 to 16 MHz balanced reference quartz oscillator, the PLL permits precise
setting of the frequency of the tuner oscillator through a 9 bit programmable reference divider ratio.
The tuning process is controlled by a microprocessor via I2C bus. A flag is set when the loop is locked.
2
The lock flag can be read by the processor via the I C bus. By means of 4 bit programmable charge
pump current, tuner designers can choose an adequate charge pump current depending on their own
loop filter design, frequency usage, and in-out band phase noise requirement.
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Release September 2006 Ver 1.0
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4. Alignment
4.1 Alignment set-up
Sweep generator:
Rhode & Schwarz polyscope
IIC
Control
Software
RF Out
Lin. Amplifier Input
VSWR Bridge
Log. Amplifier Input
SCL SDA
power supply
Activ Detector
V
Detector
DUT
A
U AGC U TUN U B
marker generator
IF Out
PC SC
This is an example of analog tuner alignment setup. The same setup can be used to align RF
performance of DVB-T tuner. IF center frequency of 36MHz will be used for the overall alignment,
and 3 points of IF frequencies, 32, 36 & 40MHz should be monitored to align in-channel
characteristics. Instead of a Polyscope we can use any type of network analyzer which has a
conversion loss measurement function. With such a general-purpose network analyzer the system
bandwidth and sampling points of the instrument should be adjusted for best resolution.
The sweep generator is connected via a return loss bridge to the antenna input of the tuner.
Because of the balanced SAW driver output the 75 Ω detector has to be connected via a dummy
balun simulating the SAW filter input impedance to the tuner output.
This dummy balun is also used for the measurements in the test set-up.
For digital tuner alignment only IF center frequency of 36 MHz can be used
all through the alignment and measurement. The tuner is designed to cover
IF bandwidth of 8MHz between 32MHz ~ 40MHz.
to IF pins of tuner
12 pF
10 turns
2 turns
The tuning voltage of each band should not fall below 0.7 V for lowest
frequency and 28 V for highest frequency.
to 75 Ohm detector
TUA6045 Half NIM
Release September 2006 Ver 1.0
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4.2
Alignment Procedures
L104
L105 L107
L106
L601
L102
L602
L603
L202
L205
L206
L301
L308
L310
L309
L204
Presented on BOM, some coils should be pre-formed before starting alignment to align easily. Also
all the coils must be checked whether they are in the right form, not distorted abruptly.
1. Current consumption & Vt of the tuner must be monitored all through the alignment to check the
proper operation of the IC. If the current consumption is over 110mA, the IC must seem to be
damaged. IFcenter = 36MHz.
2. UHF alignment :
- Set the tuner to the highest channel of UHF band, frequency = 858MHz and then adjust L603
to have Vt = 22.7 ± 0.3V.
-
Adjust L102 for VSWR.
-
For RF curve & tilt adjust L105 first, and depending on the result, adjust L106 & L107. For
highend fine-tuning, adjust L104 a little bit. If the pre-formation of L106, L107 is OK, we need
to touch only L105 & L104.
-
Sweep the whole band or selected channels, and do a fine tune once again if necessary.
3. VHFH alignment :
- Set the tuner to the highest channel of VHFH band, frequency = 442.025MHz and then adjust
L602 to have Vt = 22.7 ± 0.3V.
-
Adjust L202 for VSWR.
-
For RF curve & tilt adjust L204 first, and depending on the result, adjust L205 & L26 a little bit.
-
Sweep the whole band or selected channels, and do a fine tune once again if necessary.
4. VHFL alignment :
- Set the tuner to the highest channel of VHFH band, frequency = 442.025MHz and then adjust
L601 to have Vt = 22.7 ± 0.3V.
-
Adjust L301 for VSWR.
-
For RF curve & tilt adjust L310 first, and depending on the result, adjust L308 & L309 a little
bit.
-
Sweep the whole band or selected channels, and do a fine tune once again if necessary.
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Release September 2006 Ver 1.0
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5. Measurement Results
6.2
Electrical Characteristics of the Tuner
Unless otherwise specified all data were measured in conditions of supply voltage of 5 V ± 5%, 3.3V
± 5% and 2.5V ± 5% with ambient temperature of 25 º C ± 5%, fref of 166.667KHz.
Parameter
Min
Typ
Max
Unit
Frequency range
VHFL
VHFH
UHF
66
162
450
IF center frequency
154
442
858
MHz
36
MHz
Frequency margin at low and high ends of each band
1.5
Supply voltages and currents
Supply voltage +3.3V Pin
Supply current +3.3 V Pin
Input connector: IEC
3
3.3
3.6
120
V
mA
RF Characteristics
Input impedance
VSWR at nominal gain and during AGC
External AGC voltage for max gain
External AGC voltage for min gain
Internal AGC voltage
5
2.95
0.5
3
3.05
V
2.8
AGC range VHFL
AGC range VHFH
AGC range UHF
60
60
50
Tuning sensitivity VHFL
Tuning sensitivity VHFH
Tuning sensitivity UHF
3
5
5
Power gain
Without LNA
With LNA
Ω
50
dB
8
23
37
MHz/V
dB
) Measured at SAWOUT
)
With IF Amplifier ) Measured at IFOUT with IF
) AGC at 2V
Gain taper in each band
Noise figure VHFL
Noise figure VHFH
Noise figure UHF
RF bandwidth (3 dB) VHFL
RF bandwidth (3 dB) VHFH
RF bandwidth (3 dB) UHF
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Release September 2006 Ver 1.0
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65
100
10
10
10
5
3.5
3
3
20
20
20
dB
dB
MHz
12
TUA6045 Half NIM
Parameter
Min
Max
Unit
55
55
55
dB
Input 1 dB compression Point
Without LNA
) Measured at SAWOUT
With LNA
)
75
60
dBuV
Input IP3 (two tone)
With LNA
With LNA
80
70
dB
) Measured at SAWOUT
)
Phase Noise 1KHz offset
10KH offset
100KHz offset
5.2
Typ
Image rejection VHFL
Image rejection VHFH
Image rejection UHF
-80
-80
-110
dBc/Hz
Frequency Response (Measurement taken at SAWOUT)
RF Frequency = 130 MHz
RF Frequency = 162 MHz
TUA6045 Half NIM
Release September 2006 Ver 1.0
RF Frequency = 154 MHz
RF Frequency = 282 MHz
13
TUA6045 Half NIM
RF Frequency = 442 MHz
RF Frequency = 450 MHz
RF Frequency = 650 MHz
6.3
RF Frequency = 858 MHz
Measurement Results
Tuning Voltage and KVCO
Tuning Voltage
40
25
20
10
5
0
0
66
146
218
298
378
450
530
610
690
770
850
Frequency (MHz)
Tuning Voltage (V)
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KVCO (MHz/V)
14
KVCO (MHz/V)
15
10
Tuning Voltage (V)
30
20
TUA6045 Half NIM
Power Gain
RF Input Level without LNA : -30 dBm
RF Input Level with LNA : -70 dBm
RF Input Level with IF Amplifier : -100 dBm
Power Gain
120
100
PG (dB)
80
60
40
20
0
0
100
200
300
400
500
600
700
800
900
Frequency (MHz)
Gain w LNA (dB)
Gain wo LNA (dB)
Full Gain (IF Out)
Noise Figure
Noise Figure
4
NF (dB)
3
2
1
0
0
100
200
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Release September 2006 Ver 1.0
300
400
500
Frequency (MHz)
600
700
800
900
15
TUA6045 Half NIM
Image Rejection without LNA
Image Rejection
90
80
70
IMR (dB)
60
50
40
30
20
10
0
0
100
200
300
400
500
600
700
800
900
Frequency (MHz)
Image Rejection with LNA
Image Rejection
90
80
70
IMR (dB)
60
50
40
30
20
10
0
0
100
200
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Release September 2006 Ver 1.0
300
400
500
Frequency (MHz)
600
700
800
900
16
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1dB Compression Point (without LNA)
1dB Compression Point
120
1dB Point (dB)
100
80
60
40
20
0
0
100
200
Input Level (dBuV)
300
Output Level (dBuV)
400
500
Frequency (MHz)
600
700
800
900
600
700
800
900
1dB Compression Point (with LNA)
1dB Compression Point
120
100
1dB Point (dB)
80
60
40
20
0
0
100
Input Level (dBuV)
200
300
Output Level (dBuV)
TUA6045 Half NIM
Release September 2006 Ver 1.0
400
500
Frequency (MHz)
17
TUA6045 Half NIM
Intermodulation Product – 3rd Order (without LNA)
Intermodulation Product - 3rd Order
160
140
120
IP3 (dB)
100
80
60
40
20
0
0
100
200
300
400
500
600
700
800
900
700
800
900
Frequency (MHz)
IIP3 (dBuV)
OIP3 (dBuV)
Intermodulation Product – 3rd Order (with LNA)
Intermodulation Product - 3rd Order
160
140
120
IP3 (dB)
100
80
60
40
20
0
0
100
200
300
400
500
600
Frequency (MHz)
IIP3 (dBuV)
TUA6045 Half NIM
Release September 2006 Ver 1.0
OIP3 (dBuV)
18
TUA6045 Half NIM
Phase Noise
Phase Noise
-75
500
-80
400
-90
300
-95
-100
200
Charge Pump
(uA)
Phase Noise (dBc/Hz)
-85
-105
-110
100
-115
-120
0
66
1kHz Offset
146
10kHz Offset
218
298
100kHz Offset
378
Charge Pump
450
530
610
690
770
850
Frequency (MHz)
6. Front end interfaces
6.1
Bus Interface
Default Bus Mode on the tuner is I2C Bus
6.4
Tuner PLL Programming
Table 8a Chip Address Organisation in I2C Mode
TUA6045 Half NIM
Release September 2006 Ver 1.0
19
TUA6045 Half NIM
Table 8b. Address Selection in I2C Mode
Table 8c. Sub-Address of Write Register
Table 8d. Sub-Address of Read Registers
Default Tuner Address of the Tuner is C0H.
TUA6045 Half NIM
Release September 2006 Ver 1.0
20
TUA6045 Half NIM
6.5
Bus Format
TUA6045 Half NIM
Release September 2006 Ver 1.0
21
TUA6045 Half NIM
Every Sub-registers write must be send within one Start-Stop cycle.
Tuner PLL control software, TUA6045 Control is also available along with the evaluation
board & the reference tuner.
6.4
Bus Timing
I2C Mode
TUA6045 Half NIM
Release September 2006 Ver 1.0
22
TUA6045 Half NIM
3 Wire Bus Mode
Bus Timing Table
TUA6045 Half NIM
Release September 2006 Ver 1.0
23
TUA6045 Half NIM
1) Cb = capacitance of one bus line in pF.
Note that the maximum tF for the SDA and SCL bus lines quoted in table above (300ns) is longer than
the
specified maximum tOF for the output stages (250ns).This allows series protection resistors to be
connected
between the SDA/SCL pins and the SDA/SCL bus lines without exceeding the maximum specified tF.
2) only for I2C bus mode.
3) only for 3-Wire bus mode.
TUA6045 Half NIM
Release September 2006 Ver 1.0
24
TUA6045 Half NIM
6.5
Data Specification, Function and Default
Subaddress 00H, Main Divider
N Divider = (Frf + Fif)/Fref
e.g.
Frf = 450 MHz
Fif = 36 MHz
Fref = 166.67kHz
N Divider = (450 MHz + 36 MHz) / 166.67 kHz
= 2916
-> Register 00H = 0 0 0 0 1 0 1 1 0 1 1 0 0 1 0 0
TUA6045 Half NIM
Release September 2006 Ver 1.0
25
TUA6045 Half NIM
Sub-Address 01H, Control Byte
TUA6045 Half NIM
Release September 2006 Ver 1.0
26
TUA6045 Half NIM
Sub-Address 02H, Reference Divider R and Crystal Control
TUA6045 Half NIM
Release September 2006 Ver 1.0
27
TUA6045 Half NIM
Sub-Address 03H, AGC Control and IF Signal Processing Control
TUA6045 Half NIM
Release September 2006 Ver 1.0
28
TUA6045 Half NIM
TUA6045 Half NIM
Release September 2006 Ver 1.0
29
TUA6045 Half NIM
Sub-Address 04H, DC-DC Converter
Recommended DC-DC convertor Settings
Output High = 2 and Output Low = 2
DC-DC Frequency = 1MHz @ 50% Duty Cycle
DC-DC Frequency = Crystal Freq / (Output High + Output Low)
Duty Cycle = Output High / (Output High + Output Low) * 100
e.g. Crystal Frequency = 4 MHz
Output High = 2 ; Output Low = 2
DC-DC Frequency = 4 MHz / (2 + 2)
= 1 MHz
Duty Cycle = 2 / ( 2 + 2 ) * 100
= 50 %
Recommended Registers Settings
Reg
00H
01H
02H
03H
04H
MSB
0
0
0
0
1
14
0
1
0
0
0
13
0
1
1
1
0
12
0
1
1
0
0
TUA6045 Half NIM
Release September 2006 Ver 1.0
11
1
1
0
0
0
10
0
1
0
0
0
9
1
0
0
0
1
8
1
0
0
0
0
7
0
0
0
0
1
6
1
0
0
1
0
5
1
0
0
0
0
4
0
0
1
0
0
3
0
1
1
0
0
2
1
0
0
0
0
1
0
0
0
1
1
LSB
0
1
0
0
0
30
TUA6045 Half NIM
Sub-Address 06H, Mode Byte, Test Mode and Standby Control
Register 06H must be send first in order to Initialize the Tuner first before sending the write
registers. Setting register 06H to 00H will initialize the tuner.
TUA6045 Half NIM
Release September 2006 Ver 1.0
31
TUA6045 Half NIM
7. BOM of Infineon TUA6045 Half NIM Ver 2.1
Designators
C001
C002
C003
C004
C005
C006
C007
C008
C009
C101
C104
C105
C106
C107
C108
C109
C110
C111
C114
C117
C119
C120
C121
C122
C202
C204
C205
C206
C207
C208
C209
C210
C211
C214
C215
C217
C218
C220
C221
C304
C305
C306
C307
C308
C310
Comment
43p
36p
91p
56p
51p
220p
3n3
3n3
10n
3p9
4n7
4n7
470p
1n
4n7
4n7
1p2
100p
39p
33p
27p
27p
4n7
15p
0p5
4n7
1n
4n7
4n7
4n7
4n7
4n7
2p2
220p
4n7
220p
4n7
470p
470p
4n7
4n7
4n7
4n7
120p
4n7
TUA6045 Half NIM
Release September 2006 Ver 1.0
Footprint
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0603
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0603
0402
0402
0402
0402
Tolerance
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
Manufacturer
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
32
TUA6045 Half NIM
Designators
C311
C312
C314
C401
C408
C409
C410
C411
C412
C413
C415
C416
C417
C418
C419
C501
C502
C503
C504
C505
C506
C507
C508
C509
C510
C601
C602
C603
C604
C605
C606
C607
C608
C609
C610
C611
C612
C613
C614
C615
C616
C617
C618
C619
C620
C801
Comment
0p5
560p
470p
1n
100p
100p
1n
1n
1n
1n
39p
39p
1n
220n
100p
4n7
24p
24p
16p
16p
18p
1n
1n
2p7
2p7
2p7
2p2
100p
1p5
1p5
82p
1p2
1p2
1p2
1p2
22p
10n
4n7
6n8
33p
4n7
4n7
4n7
22n
0p5
100n
TUA6045 Half NIM
Release September 2006 Ver 1.0
Footprint
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0603
0402
0402
0402
0402
0603
0603
0603
0402
0805
Tolerance
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
Manufacturer
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
Murata
33
TUA6045 Half NIM
Designators
C802
C803
C804
C805
C806
C809
R001
R002
R003
R004
R005
R102
R103
R104
R105
R106
R109
R202
R203
R204
R205
R206
R208
R210
R301
R303
R304
R305
R306
R308
R309
R404
R405
R406
R501
R502
R502*
R503
R503*
R601
R602
R603
R604
R605
R606
R607
Comment
4n7
4n7
100p
100p
100n
100n
27k
330R
680R
10R
10R
33k
10k
51k
5R6
33k
33k
33k
33k
51k
10k
22R
33k
33k
1k8
33k
33k
51k
22R
33k
0
220R
330R
330R
1k2
0
0
0
0
12R
2k7
8R2
2k7
2k7
2k7
2k2
TUA6045 Half NIM
Release September 2006 Ver 1.0
Footprint
0402
0603
0603
0603
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0603
0402
0402
0603
0402
0402
0402
0402
0402
0402
0402
0603
0402
0402
0603
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
0402
Tolerance
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
5%
Manufacturer
Murata
Murata
Murata
Murata
Murata
Murata
34
TUA6045 Half NIM
Designators
R608
R609
R610
R801
R802*
Designator
L001
L002
L003
L101
L102
L103
L104
L105
L106
L107
L108
L109
L201
L202
L203
L204
L204
L205
L206
L209
L302
L303
L307
L308
L309
L310
L401
L402
L501
L502
L503
L504
L601
L602
L603
L605
Comment
150k
100k
33k
0
33k
Footprint
0402
0402
0402
0402
0402
Tolerance
5%
5%
5%
5%
5%
Diameter of
Wire
Diameter of Coil
Murata
Murata
Murata
0.3
1.6
0.315
1.6
100nH 0603 Murata
5
0.4
1.7
3
0.4
1.9
2
0.5
1.6
2
0.5
1.6
4
0.4
1.7
4
0.4
1.7
9
0.3
2
6
0.3
1.6
270nH 0805 Murata
4
0.4
2
4
0.4
1.6
4
0.4
1.6
8
0.3
2
8
0.3
2
390nH 0805 Murata
3u9H
0805 Murata
0R 0805
15
0.3
2
15
0.3
2
8
0.3
1.6
1u2H 0805 Murata
1u2H 0805 Murata
470nH 0805 Murata
470nH 0805 Murata
560nH 0603 Murata
1u2H 0805 Murata
15
0.3
1.9
4
0.4
1.9
2.4
0.4
1.5
1u2H 0805 Murata
No of Turn
390nH 0805
390nH 0805
1u2H
0805
6
3.5
TUA6045 Half NIM
Release September 2006 Ver 1.0
Manufacturer
Direction
CCW
CW
CCW
CCW
CW
CCW
CW
CW
CCW
CCW
CW
CW
CCW
CCW
CCW
CW
CW
CCW
CW
CW
CW
35
TUA6045 Half NIM
Note1) All the coils are full-turn types. The Unit of the Diameter of Coil & Wire is 'mm'.
Full-Turn, CCW
Note1) R502 and R503 : IF Out Pin of Tuner connect to SAWOUT of Tuner IC.
R502* and R503* : IF Out Pin of Tuner connect to IFOUT of Tuner IC
R801 used for Internal RF AGC
Note2) Pre-form. value is the distance between each turn of the coils. The pre-formation of
coils should be done before alignment by a coil manufacturer or by line workers.
Part
IC1
TR101
TR231
TR601
D601
VD11
VD12
VD13
VD14
VD21
VD22
VD23
VD24
VD25
VD31
VD32
VD33
VD34
VD35
VD36
DZ601
Q1
F501
Semiconductor
TUA6045
BF5030W
BG5130RW
BC847BW
BAS70-04W
BB565
BB565
BB565
BB565
BB565
BB659C
BB659C
BB659C
BB659C
BB565
BB689
BB565
BB6589
BB6589
BB6589
BZX384-C33
4MHz
X7359D
TUA6045 Half NIM
Release September 2006 Ver 1.0
Package
Company
VQFN-48
SOT343
SOT343
SOT323
SOT323
SCD80
SC79
SCD80
SC79
SCD80
SC79
SCD80
SC79
SCD-80
SC79
SCD-80
SC79
SCD-80
SC79
SCD-80
SC79
SCD-80
SC79
SCD-80
SC79
SOD-80
SC79
SCD-80
SC79
SCD80
SC79
SCD80
SC79
SCD80
SC79
SOD323
5mm Pitch
DOC14
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Infineon Technologies AG
Philips Semiconductor
NDK
EPCOS
Ordering Code
36
1
2
3
4
5
6
8
7
C613
1u2H L401
L003
R607
R606
R605
R604 2k7
C009
39p
5R6 33k
40
L107
R109
33k
39
C121
L501 470nH
4n7
L502 470nH
38
4n7
37
L208
L205
MIX_OUT
1n
BB565
VD22
1
5
6
BB659C
R202
1
5
6
3
2
4
L202
C307
C204
R203
4n7
C508
GND
12
11
C610
C609
C507
10
9
8
GND
-SAW_OUT
VCC
SAW_OUT
C415
39p
1n
C411
1n C410
18p
560nH
R502* 0
R503 0
R503* 0
18
R609 100k
C614
19
C615
33p
6n8
C409
20
100p
21
22
23
24
Q401
C416
39p
C412
1n
C413
C
330R
T601
C616
L206
220p
4n7
L604
L207
220p
100uH
C221
BC847BW
BAS70-04
470p
4n7
3
2
4
D601
4n7
C619 22n
PRINTED
C310
C617
3u9H
C308
120p
C210
C314
4n7
R308
4n7
33k
17
33k
T231
BG5130R
L303
33k
R502 0
16
C217
C214
22R
C205
C408 100p
15
R406 330R
C218
R306
VD21
L201
PRINTED
VD24
C215
4n7
51k
14
1n
R405
BB659C
PRINTED
R208
33k
C208
R204
51k
0p5
X_OUT
2p7
13
R210
10k
R305
C202
16p
470p
VD23
BB659C
4n7
R205
C207 4n7
16p
X_BUF
D
C509
C510 2p7
22R
4n7
L203
270nH
C206
C306 4n7
-OSC_HIGH_IN
DC_CLOCK
-MIX_OUT
7
8
-OUT
L503 C506
24p
2p2
C209
R206
C503
C220
OSC_HIGH_OUT
-OSC_HIGH_OUT
DAC3
C418
L204 PRINTED
7
6
5
OSC_HIGH_IN
GND
36
C211
C504
C505
VDD
DAC2
PRINTED
C502 24p
CHARGE PUMP
IC401
TUA6045
DAC1
C501
4n7
C
F501
X7356POUT
-IN
2,4,6,9,11,13
BB659C
C608
1p5 VD25
1p5
RF_GND
150k
4MHz
41
X_IN
C120
27p
TUNING VOLTAGE
BUS MODE
42
33p
IF_OUT
LOW_IN
R608
25
43
L108
R105
C109
BB565
-MID_IN
26
4.7n
C117
C114
R106
4n7
PRINTED
44
IF_AGC
CAS/EN
BB565
VD13
IF_IN
-IF_IN
-IF_OUT
SCL
100p
2
1
C108
VD12
IN
L504
1u2H
1n
MID_IN
27
C104
C111
-HIGH_IN
28
10R
51k
45
SDA
10R
BF5030W
R104
33k
46
RF_AGC_BUF
R005
27p
L104
L103
RF_AGC
L102
R004
L106
L105
1p2
3
OSC_MID_IN
15p
1n
OSC_MID_OUT
R102
C107
29
51p
C122
220n 30
56p
PRINTED
P0
C005
VD11
BB565
HIGH_IN
TUA6041
C004
L101
OSC_LOW_IN
31
390n
4
T001
BFP420
1n
1p2 1p2 1p2 1p2
32
390n
47
P1
C003
91p
L002
C119
P2/VRF
36p
2
C002
L001
100uH
43p
1
14
L603
2p7
48
L109
C110
1
680R
C001
C601
PRINTED
T101
OSC_LOW_OUT
470p
OSC_GND
R103
10k
C106
SAW_IN
C101 3p9
3n3
-SAW_IN
220p
R003
C602
0p5
2p2
4n7
C007
RF INPUT
BB689
C105
330R
C006
L004 82nH
33
R002
27k
C611 BB565
22p
C607
L601
C620
C612
22n
100p
VD14
C605
VD36
35
R001
8R2
L602
C604
3n3
C606
82p
R603
R602
2k7
3
C603
100p
34
R601
12R
2k7 C419
2k7
4
10n
C008
D
2k2
4n7
1u2H
4n7
470p
33k
C618
L304
VD33
BB565
L305
VD34
R311
1u2H
0
DZ601
VD35
C311
L605
4n7
R610
4n7
33k
BZX384-C33
0p5
BB689
BB689
R309
B
B
L402
0
GND
C417
1n
L306
1u2H
C401
1n
C312
560p
R301
1k8
VD31
BB565
L301
C305
4n7
VD32
R303
L302
390n
33k
BB689
C303
R801
4n7
R304
R803
33k
220R
33k
R802*
33k
C802
C801
C809
C804
100n
C810
C807
1n
1n
C806
100n
Infineon Technologies Asia Pacific Private Limited
8 Kallang Sector
Department of COM Tuner System
9th Floor of West Wing
Singapore 349282
3-Band DVB-T Half NIM with TUA6041 (Electronic Alignment)
#11_-IF_OUT
#10_IF_OUT
#9_IF_AGC
#8_GND
#7_n.c.
100n
#6_+3.3V
#4_SCL
#5_SDA
C805
100p
100p
#3_n.c.
#1_AGC Test
A
#2_Tuning Voltage Test
4n7
Size
A2
FCSM No.
Scale
A
DWG No.
1
Rev
1.0
Sheet
1 of 1
1
2
3
4
5
6
7
8
TUA6045 Half NIM
8.2 Pin Layout & Outline Dimensions
To give an impression of the real sized tuner, a photo of the tuner sample with the pin-out given in mm.
55mm
Ant Input
35mm
1
Picture of the Tuner without Covers
Pin
1
2
3
4
5
Description
RF AGC Monitoring
Tuning Voltage Monitoring
n.c.
SCL
SDA
Pin
6
7
8
9
10
11
Description
+3.3 V
n.c.
GND
IF AGC Input
IF OUT – P
IF OUT – N
Half NIM Pinning
TUA6045 Half NIM
Release September 2006 Ver 1.0
40
TUA6045 Half NIM
9. Automatic Tuner Test Set-up of the Team
This automatic tuner set-up consists of the following RF measurement equipment:
Hewlett-Packard 8970B noise meter
Hewlett-Packard 5305A frequency counter
Hewlett-Packard 8561E spectrum analyzer
Rhode&Schwarz FMA modulation analyzer
Rhode&Schwarz NGPS voltage supply(2x)
Rhode&Schwarz URV5 milivolt meter
Marconi Instruments 2031 signal generator (2x)
Marconi Instruments 2024 signal generator(2x)
All these instruments are controlled via the IEE bus by a tuner test software from a PC.
Test data will be attached to every sample tuner that is available on request.
Tuner
Test
Software
polyskop
signal generator 1
f1 MHz
signal generator 2
f2 MHz
noise figure meter
Device Under Test
3 8
4 .8
power supply
V
A
modulation analyzer
power supply
V
A
4 3 .5
Milivolt meter
frequency counter
spectrum analyzer
TUA6045 Half NIM
Released September 2006 Ver 1.0
41
TUA6045 Half NIM
Information on the Web
1. Infineon Homepage
http://www.infineon.com/
2. Ordering Info.
http://www.infineon.com/business/techlit/ordering/index.htm
3. Analog & Digital Tuner ICs Info.
http://www.infineon.com/cgi/ecrm.dll/ecrm/scripts/prod_cat.jsp?oid=-8036
4. Tuner MOSFETs & Varicap Diodes Info.
http://www.infineon.com/cgi/ecrm.dll/ecrm/scripts/prod_ov.jsp?oid=26213&cat_oid=-8960
http://www.infineon.com/cgi/ecrm.dll/ecrm/scripts/prod_ov.jsp?oid=26227&cat_oid=-8960
http://www.infineon.com/cgi/ecrm.dll/ecrm/scripts/prod_ov.jsp?oid=26231&cat_oid=-8960
http://www.infineon.com/cgi/ecrm.dll/ecrm/scripts/prod_ov.jsp?oid=13798&cat_oid=-8148
Edition September 2006
Published by Infineon Technologies AP,
8 Kallang Sector
Singapore 538211
© Infineon Technologies AG.
All Rights Reserved.
Attention please!
As far as patents or other rights of third parties are concerned, liability is only assumed for components,
not for applications, processes and circuits implemented within components or assemblies.
The information describes the type of component and shall not be considered as assured characteristics.
Terms of delivery and rights to change design reserved.
Due to technical requirements components may contain dangerous substances. For information on the
types in question please contact your nearest Infineon Technologies Office.
Infineon Technologies AG is an approved CECC manufacturer.
Packing
Please use the recycling operators known to you. We can also help you – get in touch with your nearest
sales office. By agreement we will take packing material back, if it is sorted. You must bear the costs of
transport.
For packing material that is returned to us unsorted or which we are not obliged to accept, we shall have
to invoice you for any costs incurred.
Components used in life-support devices or systems must be expressly authorized for such
purpose!
Critical components 1 of the Infineon Technologies AG, may only be used in life-support devices or
systems 2 with the express written approval of the Infineon Technologies AG.
1
A critical component is a component used in a life-support device or system whose failure can
reasonably be expected to cause the failure of that life-support device or system, or to affect its safety or
effectiveness of that device or system.
2
Life support devices or systems are intended (a) to be implanted in the human body, or (b) to support
and/or maintain and sustain human life. If they fail, it is reasonable to assume that the health of the user
may be endangered.
TUA6045 Half NIM
Released September 2006 Ver 1.0
42