DESIGN OF RESONANT CIRCUITS BASED EMBEDDED
CONTROLLER FOR POWER SUPPLY OF LCD TV AND
MONITOR
A thesis submitted in partial fulfillment of the requirements for the degree of
BACHELOR OF TECHNOLOGY
IN
ELECTRONICS AND INSTRUMENTATION ENGINEERING
By
PARUL PRADHAN
108EI002
Under the guidance of
Prof. K. K. Mahapatra
Department of Electronics and Communication Engineering
National Institute of Technology, Rourkela
May, 2012
DESIGN OF RESONANT CIRCUITS BASED EMBEDDED
CONTROLLER FOR POWER SUPPLY OF LCD TV AND
MONITOR
A thesis submitted in partial fulfillment of the requirements for the degree of
BACHELOR OF TECHNOLOGY
IN
ELECTRONICS AND INSTRUMENTATION ENGINEERING
By
PARUL PRADHAN
108EI002
Under the guidance of
Prof. K. K. Mahapatra
Department of Electronics and Communication Engineering
National Institute of Technology, Rourkela
May, 2012
2
DEPARTMENT OF ELECTRONICS AND COMMUNICATION ENGINEERING
NATIONAL INSTITUTE OF TECHNOLOGY ROURKELA
CERTIFICATE
This is to certify that the thesis entitled “Design of resonant circuits based Embedded
Controller for power supply of LCD TV and Monitor” submitted by Parul Pradhan
(108EI002) in partial fulfilment of the requirements for the award of Bachelor of Technology
in Electronics and Instrumentation Engineering at National Institute of Technology Rourkela
is an authentic work under my supervision and guidance. To the best of my knowledge, the
matter embodied in this thesis has not been submitted to any other University/Institute for the
award of any degree or diploma.
Date: 14.05.2012
Prof. K K Mahapatra
Place: Rourkela
Department of ECE
National Institute of Technology, Rourkela
Rourkela, Orissa-769008 India
1
ACKNOWLEDGEMENT
This thesis was kept on track and been seen through to completion with the support of numerous
people and I would like to take this opportunity to express my gratitude to all of them. First I
wish to express my sincere gratitude to my supervisor, Prof K K Mahapatra, for being a constant
source of encouragement and support throughout the course of this project work. His immense
knowledge, technical skills and human values have been a source of inspiration to me.
I am indebted to all the people in the Embedded System lab. Their constant support and help
during difficulties made my work easier.
I would also like to thank my friends who made this journey of completion of thesis a memorable
one. Last but not the least; I would like to thank my parents for being there for me always, and
my younger sister, whose fun-filled words were a constant source of motivation for moving
ahead.
PARUL PRADHAN
108EI002
2
ABSTRACT
Miniaturization of electronic gadgets and rapid development of technology have placed novel
challenges in front of power design engineers for an efficient delivery of power at high power
density. Next generation microprocessors will require a reductionin power consumption
which will result in lower supply voltages for these microprocessors. Thus, power conversion
will be guided by objectives such as low voltage, high power density, and high current and
high efficiency. To fulfil the requirement of smaller size units as a result of technology
scaling, high operating frequencies is the need of the hour. But such high frequencies bring
forth the problem of increased switching losses.In this work, a simple buck converter with
soft switching ZCS topology in full wave mode which includes a resonance circuit of
inductor and a capacitor is proposed to optimize efficiency and reduce switching loss at a
very high operating frequency. As high frequency operation is commanded, the size and
weight of the power supply unit practically gets reduced and thus it becomes a better
candidate for portable electronics equipment and personal digital assistants (PDAs). Also
extended battery life which is a must for such handheld gadgets is directly dependent on the
efficiency of the power conversion. Hence, a high efficiency circuit is expected to meet the
ends.The system analysis for ZCS full wave mode is presented. Its advantage over the
traditional hard switched PWM converter is well shown. The mathematical modeling of the
configuration along with its modes of operation is described extensively. The feasibility of
this circuit is supported by simulation results.
3
CONTENTS
ACKNOWLEDGEMENT .................................................................................................. 2
ABSTRACT......................................................................................................................... 3
LIST OF FIGURES ............................................................................................................ 6
LIST OF TABLES .............................................................................................................. 8
ABBREVIATIONS ............................................................................................................. 9
CHAPTER 1 INTRODUCTION ......................................................................................... 11
1.1 LITERATURE REVIEW........................................................................................... 11
1.2 MOTIVATION.......................................................................................................... 12
1.3 OBJECTIVE.............................................................................................................. 15
CHAPTER 2 TRENDS IN POWER SUPPLIES................................................................ 17
2.1 INTRODUCTION ..................................................................................................... 17
2.2 POWER SUPPLY AND ITS TYPES......................................................................... 17
2.3 LINEAR VOLATGE REGULATOR ......................................................................... 18
2.4 SWITCHED MODE REGULATOR .......................................................................... 19
CHAPTER 3 SWITCHED MODE POWER SUPPLY ...................................................... 22
3.1 GENERAL PRINCIPLES:......................................................................................... 22
3.2 THEORY OF OPERATION ...................................................................................... 24
3.2.1 INPUT RECTIFIER AND FILTER STAGE ....................................................... 24
3.2.2 INVERTER CHOPPER STAGE ......................................................................... 25
3.2.3 OUTPUT VOLTAGE RECTIFIER AND FILTER:............................................. 25
4
3.2.4 CHOPPER CONTROLLER: ............................................................................... 26
3.3 SIMULATION AND RESULTS ............................................................................... 27
CHAPTER 4 SWITCHING LOSSES AND TECHNIQUES TO
MINIMIZE
THEM
………………………………………...36
4.1 Losses across a switch: .............................................................................................. 36
4.2 Concept of Hard Switching and Soft Switching.......................................................... 39
CHAPTER 5 RESONANT CONVERTER TOPOLOGIES ............................................... 42
5.1 Introduction ............................................................................................................... 42
5.2 CONVERTER TOPOLOGIES: ................................................................................. 43
CHAPTER
6
BUCK
CONVERTER
TOPOLOGY
WITH
RESONANT
CONFIGURATION…………………………….................................................................. 46
6.1 Circuit Configuration: ................................................................................................ 46
6.2 System Analysis: ....................................................................................................... 47
6.3 Simulation Result: ..................................................................................................... 50
CHAPTER 7 SUMMARY AND FUTURE WORK .......................................................... 54
7.1 Summary ................................................................................................................... 54
7.2 Future work ............................................................................................................... 55
REFERENCES .................................................................................................................. 56
5
LIST OF FIGURES
Fig. 1.1 Current and voltage demands in processors in different generations of technology...5
Fig.2.1 Block diagram of a power supply module…………………………………………...9
Fig. 3.1 DC chopper with resistive load (a) circuit diagram (b) output voltage waveform…14
Fig. 3.2 Block diagram of a mains operated SMPS module………………………………...15
Fig. 3.3 Feedback scheme used to obtain regulation…………………………………….......17
Fig.3.4 Schematic for the forward path of power supply block…………………………….19
Fig. 3.5 Schematic of the feedback loop…………………………………………………….20
Fig. 3.6 Complete Schematic for SMPS incorporating the feedback loop………………….21
Fig. 3.7 AC mains supply input……………………………………………………………..22
Fig. 3.8 Rectified output (BLUE) and filtered output (GREEN)…………………………..23
Fig. 3.9 Input and output (RED) of the MOSFET inverter stage…………………………...23
Fig. 3.10 Voltage at output stage…………………………………………………………….24
Fig. 3.11 Pulse width modulation controller output………………………………………...25
Fig. 4.1Switching losses across a MOSFET during its transition between on and off states.29
Fig.4.2 Inevitable switching losses in conventional and resonant converters……………….30
Fig. 5.1 (a) ZC resonant switches (b) ZV resonant switches………………………………...34
Fig. 5.2 (a) Half-wave mode (b) Full wave mode…………………………………………...35
6
Fig. 6.1 Quasi resonant buck converter using ZCS configuration…………………………37
Fig. 6.2 (a) current waveform and (b) voltage waveform for zero current switching resonant
converter……………………………………………………………………………………43
7
LIST OF TABLES
TABLE 2.1 Difference between Linear Power Supply and Switched Mode Supply……….11
TABLE 3.1 Components used in the converter……………………………………………..22
TABLE 6.1 Values of circuit parameters used………………………………………………42
8
ABBREVIATIONS
VLSI
-Very Large Scale Integration
PWM
- Pulse Width Modulation
PDA
- Personal Digital Assistant
SMPS
- Switched Mode Power Supply
IC
- Integrated Circuit
NASA
- National Aeronautics and Space Administration
BJT
- Bipolar Junction Transistor
MOSFET
- Metal-Oxide-Semiconductor Field-Effect-Transistor
FET
- Field Effect Transistor
IGBT
-Insulated Gate Bipolar Transistor
ZVT
-Zero Voltage Transition
ZVS
-Zero Voltage Switching
ZCS
- Zero Current Switching
9
CHAPTER 1
INTRODUCTION
Literature Review
Motivation
Objective
10
CHAPTER 1INTRODUCTION
1.1 LITERATURE REVIEW
The concept of power supply comes under the discipline of ‘Power Electronics’ and it finds
its applications in varied fields starting from space shuttle power supplies, arc and industrial
furnaces to battery chargers and power supplies in consumer electronics. The coverage is
gigantic. We are now going to look at various generations of power supplies module starting
with the simple rectifier circuit to the revolutionary ‘Resonant Mode Power Supply (RMPS)’
and what was the reason behind its inception.
With the strict necessity for power supplies for handheld electronic equipment under various
power ratings power management faces stiff challenges. The automation in every aspect of
our livescompelsus to go for power conversion from ac to fixed dc and vice versa. Power
conversion is nowadays guided by objectives such as high current, low voltage, high
efficiency and high power density. These motives create new standards for management of
power and distribution. Attaining these objectives becomes even more challenging when low
operating voltages are to be achieved [2].
Achieving low power consumption and quality performance in digital cameras, palmtops,
MP3 players, personal digital assistants (PDAs) and other portable consumer gadgets has
long been a challenge for power supply developers. Consequently, battery life is of utmost
11
priority in portable battery-powered products, making efficiency the prime aim in the design
of thepower system. Also the necessity of small sized devices calls for increase in frequency
of operation. Thus, we have to look for options which support such high frequencies with
minimal losses. With the advent of technology scaling with each generation of
microprocessors, the supply voltage has seen a decreasing trend. Microprocessors, with
reduced power supply voltages and increased power consumption need greater amounts of
current from external power supplies, thereby posing a dire challenge on power generation
and distribution problem in today’s generation (both on chip and off-chip) .
1.2 MOTIVATION
The need for fixed dc power supply has been there since ages and a controlled one of course.
Previously, controlled dc supply could be obtained from phase controlled rectifiers. An ac to
dc rectifier operates at supply frequency of 50 (or 60) Hz. In order to obtain almost negligible
ripple in the dc output voltage, physical size of the filter circuits required is quite large. This
makes dc power supply inefficient, bulky, and weighty. Moreover, an efficiency of nearly
40% was not satisfying at all whatsoever may be the size.
All these gave way to the birth of SMPS (Switched Mode Power Supply). With the advances
in electronics circuitry and with the advent of VLSI technology, need for fixed dc power
supplies for use in ICs and digital circuits has increased manifold. For such electronic
circuits, NASA was the first one to develop a light-weight and compact switched mode
power supply in the 1960’s for use in its space vehicles. Since then Switched mode power
supplies have been the leader in the market of power supplies and have been widely used in
contemporary industrial applications and products to supply stable dc output voltage. At
present, annual production of SMPSscount for 70 to 80 % of the total number of power
12
supplies produced. The sole reason behind its success was its high efficiency of around 80%.
For clarity, SMPS are used as substitutes for the linear regulators when higher efficiency,
smaller size and light weight are required.
For many years never was the dominance of SMPS questioned mostly because of its high
efficiency. But in past few years its disadvantages started showing up which prompted people
to look for methods beyond the SMPS. Disadvantages include the generation of high
amplitude, high frequency energy that the low pass filter must block to prevent
electromagnetic interference (EMI) and a ripple voltage at the switching frequency and the
harmonic frequencies thereof. The switching currents can cause electrical noise problem also
if not carefully suppressed. Another major problem is that the switching devices in SMPS’s
are made to turn-on and turn-off the entire load at high current across the device. The devices
handling high current through them also face high voltage stresses across them. Due to these
two effects there are increased power losses in the switching devices. In case size and weight
of the converter components is to be reduced, switching frequencies are increased. At these
high frequencies, switching losses and high voltage stresses are further aggravated. The
shortcomings enunciated above were the motivations to come up with a better design where
in a converter are turned on/off when the voltage across it and/or current through it is zero at
the switching instant. It is otherwise known as ‘soft switching’.The converter circuits which
employ zero voltage and/or zero current switching are called ‘resonant converters’.
Intel founder Gordon Moore stated that the numbers of transistors per square inch in ICs
willdouble every year.This law is undeniably true even in today’s billion transistors era.The
trend has been towards lower operating voltage without
13
reducing the power
consumption.Current requirements for processors have increased exponentially over the last
4-5 years and will soon be crossing 400 A in a few decades a number of processor
applications [2].
Fig. 1.1 Current and voltage demands in processors in different generations of
technology
To achieve this high power density with high rate of increase in the number of transistors,
increased switching frequency is required.But high switching frequency results in high
switching losses in SMPS.This motivates to look for methods which promise reduction in
switching losses at such high frequencies and improve power density and efficiency of the
power supply.
14
1.3 OBJECTIVE
To develop a resonant mode power supply for LCD Monitor or LCD TV using a soft
switching technique that can optimize efficiency and switching loss at a very high operating
frequency . With this scheme there will also be a reduction in the size of filter components as
well as the overall size of the unit. The topology used will be a buck converter wherein a soft
switching technique like ZCS will be incorporated. This will lead to greater performance at
high frequencies as well as reduce current stresses across the switch.
15
CHAPTER 2
TRENDS IN POWER
SUPPLIES
INTRODUCTION
POWER SUPPLY AND ITS TYPES
LINEAR VOLTAGE REGULATOR
SWTICHED MODE REGULATOR
16
CHAPTER 2 TRENDS IN POWER SUPPLIES
2.1 INTRODUCTION
As costs of electronics decline, the power supply cost contributes a lot to the total costof
system and design effort Thus, new technology developments in power supplies are critically
important. In the past, heavy linear power supplies were used with transformers and rectifiers
from the ac line frequency to provide low-level dc voltages for electronic circuits. Late in the
1960s, use of dc sources in aerospace applications led to the development of power electronic
dc-dc conversion circuits for power supplies. In a typical power electronics arrangement
today, an ac source from a wall outlet is rectified without any transformation; the resulting
high dc voltage is converted through a dc-dc circuit to the 5V, 12 V, or other level required.
These switched-mode power supplies are rapidly substitutinglinear supplies across the whole
dimension of circuit applications.The bulk and weight of linear supplies make them infeasible
for hand-held communication devices, calculators, palmtops,mobile phones, and other such
equipment. Switched-mode supplies often take advantage of MOSFET semiconductor
technology [10].
2.2 POWER SUPPLY AND ITS TYPES
By definition, a power supply module is a device that converts the output from an ac power
line to a steady dc output or multiple numbers of outputs. The ac voltage is first rectified to
provide a pulsating dc, and then filtered to produce a smooth voltage. Finally, the voltage is
regulated to produce a constant output level despite variations in the ac line voltage or circuit
loading. These steps are shown if Fig.1.
17
Here, in this dissertation we will be concerned about the regulator part which can be either of
the two types:

Linear Voltage Regulator

Switching Regulator
Fig.2.1 Block diagram of a power supply module
2.3 LINEAR VOLATGE REGULATOR
A linear voltage regulator is a kind of regulator which uses either an active device ( such as a
BJT, FET or vacuum tube) operating in its linear region (in exchange of the saturation and
cut-off region, which are the principle operating regions in a switching regulator) or passive
devices like the zener diodes. The regulating device is made to behave like a variable resistor
connected across a current divider or voltage divider configuration, constantly altering the
divider circuit to maintain a steady constant output voltage. Two types are possible-series and
shunt [11].
It is a very inefficient method as it shed the difference in voltage by dissipating heat. Its
efficiency basically lies in the range of 20-60 %. Their application is limited to output
18
voltages smaller than the input voltage, and their power density is also low as they require
low frequency (50 or 60 Hz) line transformers and filters. However, a very high-quality
output voltage is obtained from linear voltage regulators. Their main area of usage is at lower
power levels [10].
2.4 SWITCHED MODE REGULATOR
A Switched Mode Power Supply includes a switching regulator (which works within fully on
and fully off states) in order to efficiently convert electrical power from the source side to
load side. Unlike a linear regulator, the transistor in a SMPS supply switches very quickly
(typically in the range of 60 kHz to 1MHz) between its two states. As a result, wastage of
energy is diminished to a large extent. By changing the duty cycle or the ratio of on time to
off time; voltage regulation is achieved. Whenever there is a need for higher efficiency,
lighter weight and smaller size, switching regulators are preferred over linear regulators [11].
Either output voltage or current is regulated in a switched mode power supply by switching
ideal storage elements like inductors and capacitors into and out of certain electrical modes of
operations. Converters can operate with 100% efficiency theoretically as ideal switching
elements, when ‘closed’, have no resistance across them and carry no current when ‘open’.
The comparison between linear regulated and unregulated AC-to-DC supplies with switching
regulators in general is done in the table below.
19
TABLE 2.1
Difference between Linear Power Supply and Switched Mode Supply.
Efficiency
Area of operation
Linear Power Supply
Switched mode supply
In the range of 20-60%
Lies between 80-90%
Only as step-down regulator
Used as both step up as
well as step down.
Frequency of operation
In the ac mains frequency
In
the
high
frequency
range of 50(or 60) Hz
range of several kHz to
MHz
Size and weight
Electrical noise at output
Requires
mains
frequency
Utilises
high
transformer. Hence, heavy
transformer.
and bulky
small in size.
Little or no electrical noise
Generate
noise
if
frequency
Therefore,
considerable
not
properly
designed.
Power level
Suitable
for
applications
<
20W
More suitable for large
power operations
20
CHAPTER 3
SWITCHED MODE POWER SUPPLY:
OPERATION AND SIMULATION
GENERAL PRINCIPLES
THEORY OF OPERATION
SIMULATION AND RESULTS
21
CHAPTER 3 SWITCHED MODE POWER SUPPLY
3.1 GENERAL PRINCIPLES:
In the design of power supplies, the cost and performance of the regulator is guiding factor
for choosing the type of regulator that should be used in a specific design. In order to do this
selection of an apt regulator in the designing phase, it is necessary to understand the
requirements of the application and then finalise on the selection. Advantages and
disadvantages of both types of regulators have already been jotted down in the previous
chapter. That will make this work of selection much more hassle free.
The switched mode power supply uses a switch (circuit element) to generate a regulated dc
output voltage from an unregulated one. The switch employed is turned ‘ON’ and ‘OFF’
(referred as switching) at a high frequency.When the switch is in ‘ON’ mode,it is in
saturation mode with negligible voltage drop across the collector and emitter terminals of the
switch In contrast, while in ‘OFF’ mode,it is in cut-off mode with negligible current through
the collector and emitter terminals.The ON and OFF durations are suitably controlled such
that the average dc voltage applied to the output circuit equals the desired magnitude of
output voltage. This is the basic chopper principle on which SMPS is based.
To understand this better consider the following scheme. A dc voltage source, Vs is
connected as input in series with a switch S and a load resistance, R. The switch is considered
to have unidirectional voltage- blocking capabilities and unidirectional current conduction
capabilities. If, however, an anti-parallel diode is connected across the switch, we get bidirectional properties. Fig. 2 depicts the schematic of this simple step down dc chopper.
22
Fig. 3.1 DC chopper with resistive load (a) circuit diagram (b) output
voltage waveform
The switch is being operated at a duty ratio, D which is defined as the ratio of ‘ON’ time to
the sum of the ‘OFF’ time and ‘ON’ time i.e.
D≡
=
Where, T is the time period of the switching pulse [10]. For constant frequency of operation,
T= 1/f.The output voltage so obtained is given as
23
Vo =
×Vs = DVs
3.2 THEORY OF OPERATION
The basic block diagram of a SMPS module is shown below following which there is a
detailed description of the various blocks used in it.
Fig. 3.2 BLOCK DIAGRAM OF A MAINS OPERATED SMPS MODULE
3.2.1 INPUT RECTIFIER AND FILTER STAGE
This stage is required only when the input supply is from ac mains. If input is itself in DC
then there is no need of this stage. When input is ac in nature, the first thing that is done is
conversion from ac to dc voltage. This step is known as rectification. The rectifier generates
an unregulated DC voltage which is then sent for filtering with a filter capacitor of nominal
value. As the DC passes through the rectifier stage unchanged, an SMPS designed for AC
mains input can often be used for a DC supply. However, this kind of use may prove to be
detrimental for the rectifier stage as this configuration in full load condition will only use half
24
of diodes in the rectifier. As a result, it may lead to overheating of these components, and
cause premature failure of the components. For correcting the power factor, the designer
should employ special control techniques to force the average input current to follow the AC
input sinusoidal voltage [11].
3.2.2 INVERTER CHOPPER STAGE
This stage converts the DC voltage fed to it, either directly from the input supply or from the
rectifier and filter stage, to an AC voltage by passing in through a switch like MOSFET,
IGBT. MOSFETs have high current handling capacity and have low on resistance. The
switch is regulated at a very high frequency range of several kHz. This gives the added
advantage of making it inaudible for human perception.The pulses for switching this stage
comes from a PWM controller which gives output pulses depending on the feedback obtained
from output voltage. Thus, the scheme is tightly controlled with the inclusion of feedback
loop. More on the feedback loop will be discussed later. Due to the high frequency of
application, the output transformer so used will be a high frequency type and will have small
size. This transformer is used when it is required that the output be isolated from the input,
which is the usual case.
3.2.3 OUTPUT VOLTAGE RECTIFIER AND FILTER:
If Dc output is required at the output end, the voltagefrom the chopper stage needs to be
rectified. The diodes used here will not be the normal diodes used in the previous rectifier
circuit used at the input. Here, the diodes that shall be used should be suitable for high
frequency operation. Thus, we use fast switching diodes. Also, silicon diodes are used for
high voltage of 10V or above. For lower voltages schottky diodes are used. The rectified
25
output is then passed through filters consisting of inductors and capacitors to give smooth
output. The values and size of these filter elements will be small as a result. Non-isolated
types are even simpler as they consist of inductors instead of transformer.
3.2.4CHOPPER CONTROLLER:
The chopper controller basically controls the chopping frequency of the inverter stage based
on the output voltage sensed by it. The feedback loop provides a closed loop condition,
thereby, yielding a regulated output voltage at the output stage. We use a PI controller to
respond to error signal produced, as result of difference between the measured output and
expected output, which will generate control signal for PWM controller. As result of this, the
width of the pulse energizing the chopper will vary and desired output pattern will be
obtained. Hence, voltage regulation will be achieved. The exact scheme used in this work for
feedback control is shown below.
Fig.3.3 Feedback scheme used to obtain regulation
26
3.3 SIMULATION AND RESULTS
Here, in this project we first try to design the first part i.e. a switched mode power supply
with hard switching and then incorporate within it a soft switching methodology possibly a
ZCS(Zero Current Switching ) scheme to result in highly efficient resonant mode power
supply.We use MULTISIM simulation software provided by NI Circuit design Suite product
line. MULTISIM is the schematic capture and simulation program designed for schematic
entry, simulation and feeding to downward steps such as PCB layout. It also includes mixed
analog/digital simulation capability.
In the first half of the project we design a basic SMPS isolated buck converter topology and
check for its operation as a voltage regulator. In this method, switching of the MOSFET is
done with the help of PWM controller. As a result, the circuit undergoes hard switching.
There are a lot of advantages of using PWM converters such as less component count,
constant frequency operation, high efficiency,commercial availability of integrated circuit
controllers, comparatively simple control and ability to achieve high conversion ratios for
both step upand step-down applications. However, a major disadvantage of PWM converters
is that rectangular voltage and current waveforms of the PWM cause switching losses (or
turn-on and turn-off losses) in semiconductor devices. Unfortunately this practicallylimitsthe
operating frequency range of the converter to hundreds of kilohertz. Additionally, rectangular
waveforms also generate EMI.
We disintegrate the entire circuit into parts and do designing in an organised manner to make
the debugging easier. First, we construct the forward part i.e. without any feedback. Obtain
an output, vary the load from our specified min to max range and observe the output. This
27
variation in output will then be used to give reference signal in the error amplifier used
thereafter. Next we do the feedback loop for which we first design out PI controller and
examine its proper operation. Then we incorporate it within the feedback loop and see if
PWM regulation is obtained properly or not. On getting satisfactory results we club the entire
circuit together and look for the results. The results so obtained are shown below.
Fig.3.4 SCHEMATIC FOR THE FORWARD PATH OF POWER SUPPLY BLOCK
Next we design the feedback loop part and finally present the complete circuit schematic. The
components used and their values are given in the Table 3.1.
28
Fig. 3.5 SCHEMATIC OF THE FEEDBACK LOOP
29
Fig. 3.6 COMEPLTE SCHEMATIC FOR SWITCHED MODE POWER SUPPLY
INCORPORATING THE FEEDBACK LOOP
30
TABLE 3.1 COMPONENTS USED IN THE CONVERTER
COMPONENT
VALUE
Mains Transformer,T1
50Hz, 1 Amp , TS_vitual 9-0-9V
Rectifier Diode; D1,D2,D3,D4
IN4007
Filter Capacitor,C1
100uF
Load resistance, R1
1kΩ
MOSFET Switch, Q1
IRF510
High Frequency Transformer,T2
Iron core Xformer
Switching Diodes,D5,D6,D7,D8
IN4148
High frequency Capacitor
1uF
Error amplifier,U1
UA741CD
Differential Amplifier,U2,U3,U4
UA741CD
PWM Comparator, U4
LM311H
SIMULATION RESULTS:
Fig. 3.7 AC MAINS SUPPLY INPUT
31
Fig. 3.8 RECTIFIED OUTPUT(BLUE) AND FILTERED OUTPUT(GREEN)
Fig. 3.9 INPUT AND OUTPUT (RED) OF THE MOSFETINVERTER STAGE
32
Fig. 3.10 VOLTAGE AT OUTPUT STAGE
After looking in the results of the forward path simulations, we observe that on varying the
load at the output, voltage levels at the corresponding points change. We calculate the
extremes of this voltage variation and take an average of that to feed into the inverting end of
the error amplifier. The non-inverting end is coming from the output voltage directly. The
error signal is fed to the PI controller which tries to integrate the errors till it becomes zero
and gives an output rectifying voltage which is used to vary the width of the pulses of the
PWM generator to be fed to the MOSFET switch. If the output voltage level falls below the
desired limit then an error signal will be generated that will be given to the PI controller to
produce the rectified signal. This signal is then the basis of generation of proper width of the
pulse. Thus, the width of the pulses in increased to meet the desired output of increasing the
output voltage levels. In this way, regulation of voltage is achieved. The schematic showing
how the PWM controller varies the width as per the magnitude and sign of the error signal is
as shown in Fig. 3.9. The PWM function is obtained using LM 311H where the carrier signal
is a triangular waveform of 50 kHz frequency.
33
Fig. 3.11 Pulse width modulation controller output
The PWM function is obtained using LM 311H where the carrier signal is a triangular
waveform of 50 kHz frequency. The inverting end of the comparator is fed with this carrier
signal whose magnitude is much larger than the input signal to be fed at the non-inverting end
of the comparator. As can be seen from the pink sketch in the schematic, the pulse width is
gradually decreasing as the error signal traverses from positive voltage towards negative side.
Thus, proper voltage regulation is done using isolated SMPS converter topology.
34
CHAPTER 4
SWITCHING LOSSES AND TECHNIQUES
TO MINIMIZE THEM
Losses across a switch
Concept of Hard Switching and Soft Switching
35
CHAPTER 4
SWITCHING LOSSES AND TECHNIQUES
TO MINIMIZE THEM
Switching mode power supplies (SMPS) have been widely used in contemporary industry
products to provide regulated dc output voltage. The traditional SMPS with hard switching
techniques has eminent large switching losses in the power switches. As such the overall
circuit efficiency is not satisfactory. To achieve a high efficiency circuit configuration, zero
voltage switching (ZVS) or zero current switching (ZCS) techniques based on resonant
circuits have been proposed over 10 years[1].
4.1 Losses across a switch:
A converter as in the SMPS consists of two types of elements: some controlled elements and
some uncontrolled ones like the diodes.While the controlled device is forced to turn-on or off,
the other device mainly functions as a slave to the controlled device. Power loss in the
converter, which directly affects the efficiency, is due to a combination of losses in these
devices. The losses due to each of these devices contribute individually to the rise in
temperature of the integrated converter module. Thus, in our circuit shown in the previous
chapter, MOSFET and the diode cause the maximum power loss in the configuration [12].
There are two kinds of losses that primarily are seen in these devices:

Conduction loss

Switching loss
We will discuss these two losses from the point of view of MOSFET and diode.
36
CONDUCTION LOSS:
The MOSFET and the diode behave as switches that channel current through the circuit
during each switching interval. Conduction loss is generated across these devices when they
are conducting current or when they are in ‘ON’ state. Thus, conduction loss occurs across a
MOSFET due to its ‘ON’ resistance, RDSon and across a diode due to its forward voltage drop.
MOSFET conduction loss (Pconduction (MOSFET))over the switch on-period can be approximated
as the product of RDS (ON),the average MOSFET current (IMOS (AV))and the
Duty cycle (D).
Pconduction (MOSFET) = IMOS (AV) ×RDS (ON)× D
Diode conduction loss is dependent on forward voltage (VF) whose value is large. As a
result, diodes’ conduction loss is more than that of MOSFETs. Diode loss is proportional to
VF, forward current, and conduction time (1-D) as the diode conducts when the MOSFET is
off. Therefore, diode conduction loss (Pconduction(DIODE)) is given approximately as:
Pconduction (DIODE) = IDIODE (ON) × VF × (1 - D)
Thus, the longer the ‘ON’ period, higher are the conduction losses in the devices.
SWITCHING LOSSES:
Switching losses occurs in a device during its transition between ‘ON’ state and ‘OFF’ state.
Since some time is required for changing of states in the devices, there is an inevitable
overlap between voltage and current waveforms which eventually leads to power losses in the
37
respective devices. These losses appear as power spikes in the power waveform. This is
depicted in the following figure.
Fig. 4.1 Switching losses across a MOSFET during its transition between on and off
states
In early days of power electronics, conduction losses were the main source of headache for
the power supply designer. But with the advent of technology, fast converters with smaller
size were the order of the day. Naturally, all these called for high switching frequencies
which resulted in higher switching losses as the switching loss is directly proportional to
switching frequency. As a result, in this present scenario, switching loss become dominant
and cause rise in the device junction temperature.Novel techniques are entertained to obtain
clear turn-on and turn-off of these devices. We will next look into the methods for controlling
these losses so as to cool down the circuit to some extent.
38
4.2 Concept of Hard Switching and SoftSwitching
Hard switching refers to stressful switching behaviour of power electronic devices [10]. It is a
standard SMPS switching methodology where the current and voltage waveforms are in same
phase thereby, resulting in large switching losses.
Soft switching, on the other hand, includes complex circuit and control method which
guarantees either current or voltage becomes zero while switching. It, consequently, results in
near zero switching losses. This difference becomes clear from the following diagram.
Fig.4.2 Inevitable switching losses in conventional and resonant converters
Historically, SMPS systems were considered so competent relative to the traditional linear
power supplies that no one ever questioned about their switching losses. But now, as we are
transitioning towards frequencies in the Megahertz range, the issue of switching losses
becomes fresh ground of debate. These switching losses limit the maximum switching
frequencies in hard switched systems.
DEVELOPMENT TOWARDS SOFT SWITCHING:
In the 1970’s, traditional PWM converters were employed in a switched mode operation[10].
Power switches had to turn on and turn off under hard switching conditions. Power device
39
had to undergo high voltage and high current concurrently leading to high switching losses
and stress.The switching trajectory of a hard-switched device and that of a soft switched one
is shown in Fig.4.2
I
Safe Operating Area
On
Hard-switching
snubbered
Soft-switching
Off
V
Fig. 4.2 switching trajectory of hard switched and soft switched circuit
Hence, in the next decade, quite an amount of research was done towards the promising areas
of resonant converters. The main idea was to implement resonant tank circuits in the SMPS
converter configuration to create sinusoidal current or voltage waveforms. As a consequence,
Zero Current Switching (ZCS) and Zero Voltage Switching (ZVS) condition can be created
for power supplies. The reduction of switching loss and the continualrefinement of power
switches allow the switching frequency of resonant converters to reach hundreds of kHz
(typically 100kHz to 500kHz). Eventually the sizes of the circuit magnetics as well as that of
the capacitors decrease.Resonance is allowed to occur just before and during the turn-on and
turn-off processes so as to create ZVS and ZCS conditions. Other than that, they behave just
like conventional PWM converters.
40
CHAPTER 5
RESONANT CONVERTER
TOPOLOGIES
INTRODUCTION
CONVERTER TOPOLOGIES
41
CHAPTER 5 RESONANT CONVERTER TOPOLOGIES
5.1 Introduction
Electronic power conversion technology has matured around two fundamentally different
circuit configurations: duty cycle variation, commonly known as Pulse-Width Modulation
(PWM), and resonance. The PWM technique processes power by interceding the power flow
and manipulatingthe duty cycle, thereby, resulting in continuously pulsating current and
voltage waveforms. The resonant technique processes power in a sinusoidal form.Due to
simplicity in circuit and ease of control, the PWM technique has been used substantially in
today's power electronics industry, especially, in low-power applications [4]. Resonant
converters, in contrast, have not been a preferred choice in the low power dc to dc converters
simply because of its circuit complexity.To improvise the switching behaviour of
semiconductor devices in power converting circuits, two techniques were put forth. The first
one is known as the zero-current-switching (ZCS) technique.By integrating an LC resonant
tank circuit, the current waveform of the switching device is guided to oscillate in a quasisinusoidal manner. As a result, during both turn on and turn off process, zero-currentswitching conditions are generated.This new family of circuits can be viewed as a hybrid of
PWM and resonant converters.This LC tank circuit is placed near the power switch and is
used for shaping the current and voltage waveforms of the power switch as well as storing
and transferring energy from the input side to the output sidejust as in conventional resonant
converters.
The second technique thus developed is known as zero-voltage switching (ZVS). Here, by
utilising a resonant tank LC circuit, the voltage waveform is altered so that zero voltage
condition exists across the switch during its turn on and turn off process. Thus, switching
42
losses are avoided. Practically switching frequencies of several Megahertz is possible with
this generation of quasi-resonant converters.
5.2 CONVERTER TOPOLOGIES:
There is on-going research to bring out innovative converter topologies. In today’s scenario,
converters with three different topologies:resonant, quasi-resonant and ZVT techniques are
used [2].
A resonant switch consists of a sub circuit constituting of semiconductor switch S1, and
resonant circuit elements Lr, and Cr. For a ZC resonant switch, inductor Lr, is in series with
switch S, toachieve zero-current switching; as shown in Fig. 5.1(a). In a ZV resonant switch,
as shown in Fig. 5.1(b), capacitor Cr, is in parallel with switch S1, to achieve the configuration
of zero-voltage switching[4].
Fig. 5.1 (a) ZC resonant switches (b) ZV resonant switches
If the ideal switch S1 is incorporated as a unidirectional switch in Fig.5.2 (a); the switch
current is permitted to resonate only in the positive half cycle. This resonant switch is,thus,
configured to operate in a half-wave mode.In contrast to this, if diode D, is connected in
43
antiparallel manner with Q1,theswitchcurrent can flow in bidirectional way and the
resonantswitch is said to operate in full-wave mode as shown in Fig. 5.2 (b).
Fig. 5.2 (a) Half-wave mode (b) Full wave mode
In a resonant switch converter, switch network containing resonant elements is used to
substitute the switch network of a PWM converter. The resulting upgraded converter merges
the properties ofthe parent PWM converter and the resonant switch network. Inclusion of
resonant tank elements, Lr and Cr, provides resonating condition to the conventional PWM
converter to experiencezero-current-switching (ZCS) and zero-voltage-switching (ZVS).
When aresonant tank consists of more than one energy storing element like an inductor or a
capacitor, then it results in a multi-resonant converter. With the combination of different
location of resonant elements, other resonant converter topologies can be designed.
In certain applications, the resonating condition is inevitable such as in high power
applications, where the transformer leakage inductance and the MOSFET switch’s junction
capacitance undergo resonance condition at certain load condition. However, it should be
noted here that resonance is obtained only at a specific load and it fails to happen at various
load conditions or where there is variation in line supply. The switching frequency variation
is a means to control the resonant converter circuit.
44
CHAPTER 6
BUCK CONVERTER
TOPOLOGY WITH RESONANT
CONFIGURATION
CIRCUIT CONFIGURATION
SYSTEM ANALYSIS
SIMULATION RESULTS
45
CHAPTER 6BUCK CONVERTER TOPOLOGY WITH
RESONANT CONFIGURATION
6.1 Circuit Configuration:
A buck converter is modified to a quasi-resonant converter incorporating Zero Current
Switching (ZCS) configuration to result in a topology as shown in Fig.6.1. A switch Q1 is
operated along with a resonant tank circuit, consisting of elements L1 and C1, to achieve zero
current switching so as to minimize switching losses and achieve high efficiency. This
converter will be a part of the buck converter used in the circuit shown in Fig. 3.6. The
regular circuit elements of a buck converter are also present as shown with the filter elements,
inductor, L2 and capacitor, C2. The state space equations for various modes are found out by
taking into account the boundary conditions. For modelling the system with the help of
MATLAB, we design the state space matrix equations for each of the modes and thereby, use
it to solve for the system output variables.
Fig. 6.1 Quasi resonant buck converter using ZCS configuration
46
6.2 System Analysis:
Before analysing the steady state behaviour of the circuit, we make the following
assumptions.

The filter inductor, L2 is having much larger value than the resonant inductor, L1.

Filter components at the output side, L2 and C2 along with the load resistance, R1;
are treated as a constant current sink together.

MOSFET switch and diode are assumed to be ideal. Thus, there is no forward voltage
drop in the conducting stage, neither is there any leakage current in the blocking
stage. Also, it is assumed that there is no time delay between the transitions from on
state to off state.
The following variables are defined for system analysis:

Resonant angular frequency, ώ = 1

Resonant frequency, f = ώ 2

System impedance, Zo =√( 1
( 1 ∗ 1)
1)
The entire cycle of operations can be divided into four stages or modes. These stages are
described below along with the supporting mathematical modelling:
We suppose that before switch Q1 isswitched on, diode D1 carries the output load current, Io
and let theresonant capacitor voltage is Vcrwhich clamped at zero. At the commencing of the
switching cycle, t = To, S1 is turned on.
47
Mode 1:-[T0-T1]
Input current, IL increases linearly and is given by the state equation
L1
= V1
Where, V1 is the rms value of voltage at the input side.
The span of this interval, Td1, is found out using the boundary condition given as
IL (0) = 0;
IL (Td1) = Io;
And, Td1= T1-T0 = L1 ∗ Io
1;
Mode 2: [T1, T2]
At time T1, when input current I1 reaches a level of Io, D1 is turned off. As a result, the
amount of current called [i1 (t)- Io] is utilised in charging Vcr. The state equations are:
C1
= i1(t);
L1
= V1-Vcr(t);
Subject to boundary conditions
Vcr(0) = 0;
I1(0) = Io;
48
Therefore,
i1(t) = Io + (V1/Zo) sinώt;
Vcr(t) = V1(1 - cosώt);
Now, depending upon whether we are using half- wave mode or full wave mode, two cases
occur. Here, in our topology we use the full wave mode as full wave modes are less load
sensitive.If a full-wave resonant switch is used, current in the circuit i1(t)will
continuetooscillateand feed energy back to input V1 through the situated antiparallel diode.
Span of this mode of operation is solved as given:
Td2 = ά / ώ;
Where ά lies in the range; 3 /2 ≤ ά ≤ 2
At time T2, Vcr can be obtained as
Vcr (Td2) = Vcb = V1(1- cos ά );
Mode 3: [T2, T3]
Switch Q1 is turned off at time instant T2. As a result, capacitor begins to discharge through
the output sink. Consequently, Vcr decreases linearly to zero. The state equation for this
mode of operation is given as:
C1
= Io;
The span of this stage is solved as Td3 with the boundary conditions;
Vcr (0) = Vcb;
49
Td3 =
∗
(
ά)
;
Mode 4: [T3, T4]
Here, the capacitor is in off state. So, diode D1 is left. Output current flows through this
diode. The duration of this mode of operation is given as Td4:
Td4 = T4-T3;
Td4= Ts-Td1-Td2-Td3;
Where, Ts= Switching cycle period.
6.3 Simulation Result:
We use MATLAB to generate the output waveforms for current and voltage across the switch
for this zero current switching topology. For doing this, we convert the state equations
described above into state space matrix of the format:
ẋ = Ax +Bu;
Y= Cx +Du;
Here, our state vector and output vector turns out to be same making it easier for calculations.
This vector is x= [I1, Vcr]T . Now, we solve the equations for each stage and find out the
value of system matrix vector A and input matrix vector B to solve the equation.
Mode 1:
A1 =
0
0
0
; B1 =
0
0
0
;
0
50
Mode 2:
0
0
A2 =
0
; B2 =
;
0
Mode 3;
A3=
0
0
; B3 = 0
0
0
0
0
;
Mode 4:
A4= 0; B4= 0;
The circuit parameters so used is given in TABLE 6.1 below.
TABLE 6.1
Values of circuit parameters used
COMPONENT
TYPE
MOSFET SWITCH, Q1
IRF510
RESONANT INDUCTOR,L1
50uH
RESONANT CAPACITOR,C1
15uF
SWITCHING DIODE,D1
BA918
FILTER INDUCTOR,L2
5mH
FILTER CAPACITOR,C2
280uF
LOAD RESISTANCE,R1
50Ω
51
The voltage and current waveforms for full wave mode zero current switching quasi resonant
convertersare given in Fig. 6.2.
(a)
(b)
Fig. 6.2 (a) current waveform and (b) voltage waveform for zero current switching resonant
converter
Thus, we see from the current waveform of the above circuit that current across the switch
becomes zero during the time interval from T2 to T4. As a result, when in these modes, we
can forcedly turn the switch on and off without incurring any sort of losses across the switch.
Thus, zero current switching is obtained which results in enhanced efficiency. Thus,
paradigm change in the efficiency is observed in soft-switched switches as compared with
hard switched ones.
52
CHAPTER 7
SUMMARY AND FUTURE WORK
SUMMARY
FUTURE WORK
53
CHAPTER 7 SUMMARY AND FUTURE WORK
The dawn of the new era in the field of consumer electronics has put forth a herculean task
before the power supply designers where the objectives of high efficiency, high power
density, low voltage and high current have become the guiding principles. High efficiency dc
to dc converters are highly essential for optimised working of various areas such as
industries, communication systems, power transmission etc. Miniaturisation in all aspects of
automotive industries requires smaller sized modules which mandatethe high operating
frequencies. But managing the switching losses at such high frequencies becomes the critical
issues nowadays which every power designer has to face. So here, in our work, we
concentrate upon methods to diminish these switching losses.
7.1 Summary
This dissertation was committed to find out solutions for step down converters operating in
high frequency region. The conventional PWM switched buck converter faces problems in
the area of switching losses when high frequencies and small size equipment is required at
the delivery side. It, therefore, abases the system efficiency and hinders with the power
quality. To attain high power density, it is mandatory that switching frequency be increased.
Increase in switching frequency results in increased switching losses. Thus, this loss
reduction is the prime aim of our work which will be achieved with the help of soft switching
techniques. The precise goal of this study can be summarised as: a step down buck converter
topology with quasi-resonant switching is done to minimize switching losses across the
device, lower the current and voltage stresses formed across it and diminish the overall size
of the device with enhanced efficiency so as to be suitable for use in high frequency circuits.
Under this scheme, the switch is turned on and off under zero resonant switching (ZCS)
54
condition where current across it is zero during transition between its two states. Therefore, it
becomes very efficient. These qualities of the converter are validated by experimental results
provided in the chapters concerned which certify that zero current is present across the switch
while it’s turned on. The circuit configuration is also simple. Moreover, it employs a
controlled feedback loop which promises accurate regulation of output voltage. Thus, soft
switching technique comes to our rescue when high frequency demand is presented by
today’s ultra-advanced electronics circuitry.
7.2 Future work
This dissertation has looked into some substantial and excellent methods in the management
of power. But a lot of future research work still needs to be done. A great area for such
research lies in the parasitic effects found in the circuit elements. Parasitic capacitances are
inevitable and undesirable effects that occur within the parts of electronic circuits simply
because of their proximity to one another. Also, at low frequencies these capacitances
generally don’t make their presence felt, but when it comes to high frequency applications,
they are a real headache. Parasitic capacitance in a MOSFET can instigate conduction
without any pulse applied to its gate. Therefore, excellent design parameters are to be
maintained to avoid this issue. The other interesting area is that of viability of the power
supply module in terms of its compatibility with the portable electronic equipment to which it
is attached. Thus, the supreme challenge is that of system integration for such power supply
module.
55
REFERENCES
[1] Lin Bor-Ren, Tseng Chao-Hsien, “ZVS half-bridge SMPS design for LCD monitor and
LCD-TV” , in International Journal of Electronics, 2008, pp. 189-204.
[2] Pattnaik S., “Development of improved performance switch mode converters for critical
load applications”, Ph. D. Dissertation, 2011, National Institute of Technology, Rourkela.
[3]MAHAPATRA K. K., GHOSH ARINDAM, JOSHI AVINASH, DORADALA S.R., “A
novel current initialization scheme for parallel resonant dc link”, International Journal of
Electronics, 2000, vol. 87, pp. 1125-1137.
[4] Fred C. Lee, “High-Frequency Quasi-Resonant Converter Technologies”, in Proceedings
of IEEE, 1988, vol. 76, no. 4.
[5] Pattnaik S., Panda A. K., Mahapatra K.K., “An Improved Multiphase Converter for
New Generation Microprocessor”, Third IEEE International Conference on Industrial and
Information Systems (ICIIS 2008), 8-10 December 2008, IIT Kharagpur, India. pp. 5.
[6]Pattnaik S., Panda A. K., Mahapatra K.K., “Analysis of Non-isolated Soft Switching DCDC Buck Converter‖, Third IEEE International Conference on Industrial and Information
Systems (ICIIS 2008), 8-10 December 2008, IIT Kharagpur, India. pp. 6.
[7]Pattnaik S., Panda A. K., Mahapatra K.K., “Experimental Validation of A Novel Zero
Voltage Transition Synchronous Buck Converter”, IEEE TENCON 2008, Hyderabad,
November 18-21. pp. 6.
[8] Pattnaik S., Panda A. K., Mahapatra K.K., “A Novel Improved Soft Switching PWM DCDC Converter‖ POWERCOIN 08, Salem, Mar 20-21, 2008, pp. 4.
56
[9]Pattnaik S., Panda A. K., Mahapatra K.K., “An Efficient Multiphase Converter for New
Generation Microprocessor‖ POWERCOIN 08, Salem, Mar 20-21, 2008, pp. 4.
[10] Rashid Muhammad M., POWER ELECTRONICS HANDBOOK, Canada, Academic
Press, 2001.
[11]Wikipedia. http://en.wikipedia.org.
[12] NPTEL. http://nptel.iitk.ac.in/
57