Practical Power Application Issues
for High Power Systems
Global Power Seminar 2006
1
Agenda
• Driving high-side MOSFETs
• Improving reliability during half-bridge switching
• Using Fairchild Semiconductor’s PFC/PWM combos
• Two switch forward converter with PFC front-end
• Brushless DC motor drive using MOSFET-based
Motion-SPM
• Motion-SPM-based motor drive with PFC-SPM front-end
2
1
Driving High Side N-channel MOSFETs
Vdc
• The high side MOSFET shown will be
switched on fully only if (Vg-Vs) is greater
than 10V
High side
switch
(N-channel)
Vg
• As Vdc is only marginally higher than Vs,
this means that Vg must be just under 10V
higher than Vdc
• A high side driving technique is needed
Vs
Load
resistor
3
High Side Driving Techniques
Driver IC
Notes
Usage
Optocoupler
Transformer
• Moderate cost
• Compact size
• High speed
• Noise immunity
• Good isolation
• Needs floating supply
• Low cost
•
•
•
•
• Three phase input systems
• Motor drive
• UPS
• Power supplies
• Compact fluorescent
lamps
Linear ballasts
600V motor drive
UPS
Power supplies
4
2
New Product Family: Opto Drivers
FOD3180 – A high speed IGBT/MOSFET gate drive optocoupler
Features
• 2A minimum peak output current
• High speed response: 200ns max
propagation delay over temperature range
• 250kHz maximum switching speed
• 20ns typical pulse with distortion
• VCC operating range: 10V to 20V
• 5000Vrms, 1 minute isolation
• Under voltage lockout protection (UVLO)
with hysteresis
• Minimal creepage/clearance of 7.0mm
• Safety agency approvals pending
5
Low Voltage Half-Bridge Driver:
FAN5109
• 12V high side and
12V low side drive
• Switching frequency above
500kHz
Sourcing
• Output disable function for
synchronizing with PWM
Sinking
High
2A typ
3.3Ω max
3A typ
1.5Ω max
Low
2.7A typ
2.6Ω max
3.5A typ
1.2Ω max
controller
6
3
High Voltage Drivers
Input Output
FSC Device
Type
90/180mA
One input
One output
High Side
Only
Two inputs
Two outputs
Common Vs connection 14 pins
High&Low
Side
Common Vs connection 8 pins
One input
Half-bridge
Two outputs
Single Output
350/650mA
FAN7361/2
(250/500mA)
FAN7384
FAN7380
FAN7382
Separated output
Resistive Dead-time
control
FAN7383
7
Function of Bootstrap Circuit – Low
Side ON
15V
DB
VCC
Up to 600V
15V-Vf
VB
3
8
CBS
HIN
2
7
ON / OFF
C O N T R O LL E R
HO
COM
LOAD
0V
4
6
L
VS
1
LIN
MOSFET
ON
5
LO
C1
LAMP
C2
0V
8
4
Function of Bootstrap Circuit – Both
OFF
15V-Vf+Vs
DB
VCC
Up to 600V
VB
8
3
CBS
HIN
2
7
ON / OFF
C O N T R O LL E R
HO
LOAD
Vs
4
COM
6
L
VS
1
C1
5
LIN
LAMP
LO
C2
9
Function of Bootstrap Circuit – High
Side ON
DB
VCC
Up to 600V
15V-Vf+Vs
VB
3
8
CBS
HIN
2
ON / OFF
C O N T R O LL E R
MOSFET
ON
7
HO
COM
6
VS
1
LIN
LOAD
Vs
4
L
C1
5
LO
LAMP
C2
10
5
Circuit Transients in Half-Bridge and
Synchronous Buck Circuits
• Both half bridge and synchronous
buck circuits are exposed to similar
kinds of transients
• Ringing on the Vs line, which can
exceed Vdc or be lower than the
ground
• This noise can be coupled through to
the VB line causing positive and
negative spikes
Channel 2: Vs voltage in
synchronous buck
11
Current Flows When Vs Ramps Up
VDS
VS
LS1
ICHGHS
RDS(ON)
ICHG = CLS
dVS
dt
VDC
CHS
VS
LS2
IL
0
t
CLS
-Vf
ICHG
12
6
Estimation of Overshoot on Vs
ICHG = CLS
VDS
fringing =
LS1
RDS(ON)
dV
dt
1
2π LLK × CLS
ICHGHS
1
1
2
2
LLKICHG = CLS VCAPMAX
2
2
CHS
where LLK = L S1 + L S2 ; damping = 0
VS
rearranging gives
LS2
VCAPMAX =
LLK
dV
× ICHG = 1/(2 × π × fringing ×
)
CS
dt
VOVERSHOOT =
CLS
ICHG
L S1
VCAPMAX
LLK
(This is a simplified analysis of a complex
third order system)
13
Estimation for Synchronous Buck
dV
= 10V/ns (from graph)
dt
fringing = 73MHz (from graph)
CLS = 1.2nF (from COSS of 2 FDS6688' s)
fringing =
1
2π LLK × CLS
LLK = 4nH
where LLK = L S1 + L S2
Channel 2: Vs voltage in
synchronous buck
VCAPMAX = 1/(2 × π × fringing ×
VOVERSHOOT =
dV
) = 22V
dt
L S1
× 22V = 11V
L S1 + L S2
14
7
Package Impedance Comparisons
Comparison of electrical characteristics of various power packages
Package
Description
Ldd
nH
Lss
nH
Lgg
nH
Rd
mΩ
Rs
mΩ
Rg
mΩ
2 x 2.5 mm BGA
0.056
0.011
0.032
0.05
0.16
0.79
4 x 3.5 mm BGA
0.064
0.006
0.034
0.02
0.06
0.95
5 x 5.5 mm BGA
0.048
0.006
0.041
0.01
0.04
0.78
FLMP ( Large 3s)
FLMP ( Large 7s)
0.000
0.744
0.943
0.002
0.245
2.046
0.000
0.921
0.002
0.137
SO-8
0.457
0.194
0.901
1.849
0.12
2.04
20.15
SO-8 Wireless
0.601
0.709
0.932
0.16
0.23
1.77
IPAK (TO-251)
2.920
3.490
4.630
0.25
0.74
8.18
DPAK (TO-252)
0.026
3.730
4.870
0.00
0.77
8.21
D2PAK (TO-263)
0.000
7.760
9.840
0.00
0.96
12.59
2.038
SO8 package inductance is around 1.5nH per package
15
Estimation for Half Bridge Driver
• The same illustrative approach
can be used to estimate the
overshoot for a half bridge
driver
dV
= 6 V / ns ( from 0.3 A int o 21nC Qgd, 400 V )
dt
CLS = 2nF ( from COSS of FCP11N60 )
LLK = 32nH ( from 2 TO220 packages )
• With a minimal inductance of
32nH, the overshoot is expected
to be 24V
• In practice, the layout
inductance could be much
higher: 150nH – 200nH
LLK = L S1 + L S 2
VCAPMAX = LLK × CLS ×
VOVERSHOOT =
dV
= 48 V
dt
L S1
× 48 V = 24 V
L S1 + L S 2
• 200nH => 60V overshoot
16
8
Analysis of Half Bridge Driver
Zoomed image
VS
HOVS
15V
600
V
Yellow curve (VS pin voltage) shows steep
slope of 60.2V/ns
For the dv/dt noise from 1V/ns to above 50V/ns, Fairchild’s HVIC
shows no malfunction
17
Robustness in Half Bridge Drivers
Add positive noise on the supply of high-side driver
• High-side supply voltage(15V) + positive pulse noise on VB
18
9
Positive Noise Immunity Test
85V
22V
Normal Condition
FAN7380M
(SMD)
Abnormal Condition
19V
Company A
(DIP)
21V
Latch & Destruction
Normal
27V
Normal
Company B
(DIP)
Abnormal Condition
28V
Latch & Destruction
Normal
Company C
(DIP)
Noisy Supply
Test condition
VBS=15V
Input signal : 5kHz, 50% duty
Noise : 1µs pulse width
HVIC Output
19
Negative Vb Noise Immunity Test
- 80V
- 31V
Normal Condition
FAN7380M
- 12V
Company A
Normal
Company B
Normal
Abnormal Condition
- 22V
Latch
Abnormal
- 12V
-24V
-1.5V
Company C
Abnormal Condition
Abnormal
Latch & Destruction
Test condition
VBS=15V
Input signal : 100Hz, 50% duty
Noise : 1µs duty
20
10
Allowable Negative Vs Voltage
Comp A
FAN7382
-10V
Fairchild
Normal Condition
Company A
Normal
-20V
Missing Pulses
-VBS
-5V
Logic Held
21
Reduced Static Power Consumption
IQCC
Comp A
IQBS
Comp A
FAN7382
FAN7382
22
11
240W Output PFC Power Supply
85V –
265VAC
input
Rectifier
PFC
Stage
Two Switch
Forward/
Half Bridge
Primary Side
Transformer
Secondary
Side
Rectification
12V,
20A
output
Rectified
input
Half
Bridge
Driver
To
Secondary
Side
PFC/PWM
Combined
Controller
23
Power Factor Correction (PFC)
• Power Factor Correction (PFC) circuits do
two things:
AC phasors
I
• Improve the AC power factor closer to 1
• Remove low frequency harmonics from
Phase angle V
the power supply
I x cos(phase angle)
• The harmonics are not in phase with the
50Hz/60Hz input voltage so they do not
Power = VI cos(angle)
Power = VI x power factor
Power factor = cos(angle)
provide any useful power
24
12
EN61000-3-2 Implications for PFC
EN61000-3-2 is a standard limiting harmonic current
• Applies to mains powered equipment sold in Europe today
– Latest specification includes amendment A14
• PFC (power factor correction) is not specifically required
• Designer is free to choose how to meet this standard:
− do nothing special for most systems
− use passive PFC (e.g. large inductors)
− use active PFC (i.e. using semiconductors)
The expected design choices depend on the system:
Lighting > 25W
active PFC using transition mode PFC
TV > 75W
active or passive PFC
PC > 75W
active PFC
Monitor > 75W
passive PFC (possibly active PFC)
Other systems
no action needed
25
Two Approaches to PFC
Transition mode:
lower cost, more EMI
Continuous mode:
higher cost, less EMI
26
13
PFC/PWM Combo Circuit
Configuration for PFC only - ML4800
27
Implementing Continuous Mode PFC
• The boost PWM controller has voltage feedback with output set to
around 385V
• An error amplifier measures this output voltage. A multiplier combines
the error voltage with the input half sinusoidal voltage
• Vrms is used as an auxiliary input to
the multiplier to remove the gain
dependency on Vrms
• The output of the multiplier is fed
into a second amplifier, which
controls the current flow using a
fixed frequency PWM controller
28
14
Implementation of Vrms and Current
Sensing
Vrms sensing
• R8/C3, R9/C7 form a two pole low pass filter
to generate the average voltage level
• R8/R9/R15 form a potential divider to divide
down the high voltage
To Isense
To Vrms
Current sense circuit
• R1 is the current sense resistor
• D5 and D6 clamp the voltage across the
sense resistor to provide protection in the case
of transients or overload conditions
29
Choice of Power Setting Components
Voltage divider network
• After selecting the desired boost
voltage, for example, 385V, set the
divider to generate 2.5V at 385V
input
Overvoltage protection
• Overvoltage protection is active when
the feedback input is more than 2.6V
to 2.8V, and the hysteresis is around
100mV
Setting the IAC resistor
• This is determined by a formula. At
the minimal input voltage, the gain
modulator has maximum gain. The
resistor should be high enough to
prevent saturation. For Vmin = 80Vac,
the resistor is around 1 MΩ
Current sense resistor
• This is determined by a formula
based on the multiplier gain and the
desired power output
• Vrms divider network
• Set to generate 1.2V on Vrms at the
minimal input voltage
30
15
ML4800 PFC Controller
240W Output PFC Circuit
Vbus
12
6
D1
ISL9R460P2
L3
FERRITE BEAD
R11
620K
~
-
L1
1.4mH
R16
820K
+
R12
620K
R17
820K
~
630V
470nF
C2
BR1
GBU6K
C3
100nF
R2
180K
C4
470nF
1
Q1
FQP13N50C
R13
100K
R15
22
0.6W
R14
20K
R19
13K
1
2
3
4
5
D10
1N4148
6
7
D12
1N4148
C23
100nF
C13
470nF
8
C8
12nF
Ieao
Veao
Iac
Vfb
Isense
Ref
Vrms
Vcc
IC1
Ss ML4800 Vo1
Vdc
Vo2
Ramp1
GND
Ramp2
Ilim
C16
470pF
C15
18nF
31
+
C55
82uF
450V
+
C56
82uF
450V
C248
100nF
C7
1.2nF
R35
100
0.6W
D11
1N4148
C5
82uF
450V
2
R7
0.12
2W
R3
180K
+
R18
10K
R24
42K
C14
100nF
25V
16
Vcc
15
14
13
12
11
C12
470nF
50V
D15
FDLL4148
10
R20
820K
9
D16
FDLL4148
R1
180K
C10
6.8nF
C9
68nF
R23
4.7K
PFC/PWM Combo Controllers
• Combine leading edge PFC and trailing edge PWM in one package
• Synchronizing PFC and PWM :
• Reduces ripple in bulk capacitor, which reduces size/quality of input
capacitor
• Increases efficiency and reduces system noise
• Increases usable PFC bandwidth - Simplifies compensation
32
16
Benefits of Leading Edge/Trailing
Edge PWM
Comparison of Leading/Trailing Edge Modulation (7a) to
Trailing Edge Modulation only (7b)
33
Selection Guide for PFC ICs
34
17
Forward Converter Using Half Bridge
Driver
Vbus
R225
D217
UF5407
Q205
Vcc
IC4
1
2
HB_In
3
4
C239
220nF
25V
FQP9N50C
22
0.25W
D216
RS1K
VCC
VB
HIN
HO
LIN
VS
COM
LO
8
C235
100nF
7
6
5
R226
22
FAN7382N
1
12
2
11
3
10
4
9
5
8
Q206
6
FQP9N50C
R234
220
D218
UF5407
R233
0.47
2W
7
TR1
TRNSFMR EVD30
2
C238
220pF
25V
1
ISense
35
Synchronous Rectification Stage on
Output
1
12
2
11
3
10
4
9
5
8
6
7
1
D220
FYPF2010
R236
1K
Sync
Q207
FDP3652
5
C242
10nF
25V
Sync
TR1
TRNSFMR EVD30
L5
40uH
9A
R237
1K
D222
BZX84C18
0.35W
C243
10nF
25V
R238
1K
+
C244
680uF
35V
+
C245
680uF
35V
+
C246
680uF
35V
2
1
CONN5
B2P-VH
FDP3652
Q208
D221
BZX84C18
0.35W
R239
1K
D219
FYPF2010
36
18
Selection of Switches and Diodes for
CCM PFC
Continuous conduction mode
• Good for higher power > 300Watts
• Fixed switching frequency generally <100kHz
• Typically hard turn-on and hard turn-off
• Soft switching approaches are sometimes used
• Low ripple current
Switch considerations
• Best boost switch tends to be a SMPS IGBT or SuperFET
• HGTG12N60A4, HGTG20N60A4, FGH30N6S2, FGH40N6S2
• FCP11N60, FCP20N60, FCH47N60
• Best diode is a Stealth diode: soft, low Qrr, fast diode
• ISL9R860P2, ISL9R1560P2, ISL9R3060G2
37
600V Stealth Diode Family
Part Number
ISL9R460P2
ISL9R460PF2
ISL9R460S3S
ISL9R860P2
ISL9R860PF2
ISL9R860S3S
ISL9R1560G2
ISL9R1560P2
ISL9R1560S3S
ISL9R1560PF2
ISL9R3060G2
ISL9R3060P2
Package Type
TO-220
TO-220F
TO-263(D2PAK)
TO-220
TO-220F
TO-263(D2PAK)
TO-247
TO-220
TO-263(D2PAK)
TO-220F
TO-247
TO-220
Current
4A
4A
4A
8A
8A
8A
15 A
15 A
15 A
15 A
30 A
30 A
Vfmax
2.4 V
2.4 V
2.4 V
2.4 V
2.4 V
2.4 V
2.2 V
2.2 V
2.2 V
2.2 V
2.4 V
2.4 V
trr max
22 ns
22 ns
22 ns
30 ns
25 ns
30 ns
40 ns
40 ns
40 ns
40 ns
45 ns
45 ns
38
19
Solutions for Two Switch Forward
Converters
Q2
D1
12V
Q3
D2
Q1
Q2
D2
Power
300W
600W
Q1
FQP18N50V2
FCP11N60
FCH20N60
FCA20N60
FDH27N50
FCH20N60
FDH44N50
Q3
Q2
Q3
D1
D2
FQP18N50V2
FDH27N50
FCP11N60
FDP047AN08A0
FDP3672
FDP3652
ISL9R860P2
RURP860
FDH44N50
FCH20N60
2 x FDP060AN08A0
FQP90N10V2
FDP3632
ISL9R1560P2
RURP1560
39
SPM-Based Power Inverter – BLDC
Motor
85V-265VAC
input
Rectifier
SPM Module
BLDC
Motor
FPS
Power
Supply
Microcontroller
DSP
Comparators
for back EMF
sensing
40
20
Motion-SPMTM (Smart Power Modules)
with MOSFETs for BLDC Motors
SPM Series
Rating
(Motor
rating)
Mini-DIP
600 V, 3~4A
(100 -200W)
3-phase IGBT inverter with
- 3 divided N-terminal for current
sensing
- Built-in HVIC with UVP
- Built-in LVIC with UVP, OCP
Air conditioners
Washing machines
Refrigerators
Industrial inverters
500 V, 2~3 A
( 50 ~ 100 W)
3-phase FRFET inverter with
- 3 divided N-terminal for current
sensing
- Built-in HVIC
- Low EMI & ruggedness
- Small footprint
Fan motors
Water suppliers
Air cleaners
44 x 26.8 mm
MotionSPM
Main
Applications
Features
Tiny-DIP
29 x 12 mm
41
New Motion-SPMTM in Tiny-DIP
Simplifying Motor Design
Low-power (under 100 W) motor market
• Fan motors for air conditioners and
air purifiers
• Water suppliers and water pumps
High voltage brushless DC (BLDC) motor
is replacing single-phase AC induction
motors
• Increased energy efficiency
from under 50% up to 90%
• Decreased acoustic noise
and vibration
• High-power density and
small volume/weight
42
21
Microcontroller
Motion-SPM in Tiny-DIP
Application Circuit
43
New Motion-SPMTM in Tiny-DIP
Simplifying motor design
Motion-SPM in Tiny-DIP enables high-voltage BLDC motor drives with
rectified AC source
Motion-SPM in Tiny-DIP enables inverter built-in BLDC Motor
• Compact package
• Low electromagnetic interference (EMI)
• Low thermal resistance
29 mm
m
12
m
44
22
Motion-SPMTM in Tiny-DIP
Block diagram
(1) COM
(2) V B(U)
(3) Vcc (U)
(4)IN (UH)
(5) IN (UL)
(6) V S(U)
(7) V B(V)
(8) Vcc (V)
(9) IN(VH)
(10) IN(VL)
(11) V S(V)
(12) V B(W)
(13) Vcc (W)
(14) IN(WH)
(15) IN(WL)
(16) V S(W)
Product Family:
P (17)
VB
Vcc
Ho
HIN
LIN
Vs
Lo
COM
• 500V/3A (RDS(on)=2.2Ω), 2A (RDS(on)=4.0Ω)
• 250V/3A (RDS(on)=1.8Ω)
U (18)
Target Applications:
NUV(19)
VB
Vcc
Ho
HIN
LIN
Vs
Lo
COM
• Small power inverters
(Air cleaner fans, air conditioner fans,
refrigerator, water suppliers)
V (20)
Features:
• High energy efficiency
• Smaller Irr / Trr Æ minimized Psw loss
• Smaller conduction loss @ low current
ÆPCON= I2R
• Good short circuit characteristics with power
MOSFET
• Very compact size
N W(21)
VB
Vcc
HIN
LIN
Vs
COM
Ho
W (22)
Lo
45
Motion SPMTM in Mini-DIP (MOSFET
SPM3)
(19) VB(W)
(18) VCC(WH)
(17) IN(WH)
(20) VS(W)
(15) VB(V)
(14) VCC(VH)
(13) IN(VH)
(16) VS(V)
(11) VB(U)
(10) VCC(UH)
(9) IN(UH)
(12) VS(U)
P (27)
VB
VCC
COM
IN
Line-up (under development)
OUT
VS
W (26)
• 500V/3A, 4A
VB
VCC
COM
IN
Target Applications
OUT
VS
V (25)
(refrigerators, fans)
VB
VCC
COM
IN
• Low cost consumer appliance inverters
OUT
VS
U (24)
Feature
• 3-phase MOSFET inverters with driver ICs
(8) CSC
(7) CFOD
(6) VFO
(5) IN(WL)
(4) IN(VL)
(3) IN(UL)
(2) COM
(1) VCC(L)
• Good thermal resistance
C(SC) OUT(WL)
C(FOD)
NW (23)
VFO
IN(VL)
NV (22)
IN(UL)
COM
VCC
• Small size & large pin-to-pin spacing with
zigzag package structure
IN(WL) OUT(VL)
• 3 N-terminals for low-cost current sensing
OUT(UL)
VSL
NU (21)
46
23
Motion-SPM in Mini-DIP
Broad Product Family
Ceramic Base
5
3Amp
5Amp
3
10Amp
DBC BASE
15Amp
2
15Amp
1
20Amp
30Amp
0
0
5
10
15
20
30
Current Rating (A)
47
Input Filters and Rectifiers
J6
2
1
VTR-250
J1
C52
472 2kV
2
VTR-250
2
RV1
R30
500k 1W
2
1
2
F1
2
SVC471D-14A
J3
1
2
L1
19mH
RT1
5D-11
4 -
P
D4
GBU6J
+ 1
+
3
4
1
t
1
1
3
2
2
1
Thermal resistance_IGBT (Degree/W)
4
C32
220u 400V
R31
1M 1W
1
5A 250V
C31
330nF AC275V
VTR-250
48
24
Auxiliary Power Supplies using FPS
1
P
T1
Trans_1916
1
6
3
3
4
+15V_PRI
1
+
C37
220uF 35V
5
U9
7805/TO
VIN
C39
105
VOUT
+5V_PRI
3
+
100uF 16V
C38
C40
105
COM
+
C42
47uF 35V
Vcc
R43
4
C46
104
R44
9k 1/8W F
R46
ISO2
3.3k 1/8W
H11A817D
3
2
U12
KA5M02659RN
1
1.8k 1/8W
5
FB
R38
6.8 1/8W
4
2
GND
Drain
Drain
Drain
Drain
1
6
7
8
D8 US1J
D7 US1J
GND
D6
US1J
8
2
2
D5
SMBJ170
R23
100k 1W
C50
333
1
2
D9
KA431A
R25
10k 1/8W
R52
1.8k 1/8W F
49
Heatsink Installation
Chassis
SPM5
PWB
Heatsink
Thermal Conductive
Silicone Adhesive
SPM5
PWB
Mounting
Heatsink
Thermal Rubber
SPM5
PWB
'P' pin
50
25
PFC-SPM Variants
VTH
RTH
CSC
CFOD
VFO
IN(S)
IN(R)
COM
VCC
VTH
NTC
Thermistor
PR
D1
D2
CSC
CFOD
RTH
OUT(S)
Q1
D3
Q2
CSC
R
CFOD
D4
IN(R)
COM
ND
OUT(R)
NR
NS
VCC
PR
D1
S
VFO
IN(S)
NTC
Thermistor
D2
CSC
S
CFOD
R
VFO
VFO
IN(S)
IN(S)
IN(R)
IN(R)
COM
COM
VCC
VCC
OUT(S)
Q1
D3
Q2
D4
N
OUT(R)
Shunt
Resistor
NSENSE
VAC-
Full switching PFC
Partial switching PFC
• Line-up :
- 600V/20A - SPM3 package with DBC
• Target Applications :
- Low/medium power consumer
appliance such as room air conditioners
• Feature :
- Good thermal resistance
- Same package as SPM3
- Built-in thermistor for temperature sensing
- LVIC with UVP, OCP
• Line-up :
- 600V/20A,30A, 50A - SPM3 package with DBC
• Target Applications :
- Medium/high power consumer appliance
applications such as room/package air conditioners
• Feature :
- Good thermal resistance
- Built-in shunt resistor
- Same package to SPM3
- Built-in thermistor for temperature sensing
- LVIC with UVP, OCP
51
PFC Module Application Slow versus
Fast Switching
Vac
PSCM
In the PSCM (partial switching converter)
module PFC approach, each IGBT is
switched once per cycle
Iac
• PFC frequency: 50/60Hz
Gate
IGBT1
Gate
IGBT2
In the PFCM, full continuous
conduction mode PFC is used
Vac
PFCM
Iac
• PFC frequency: 40kHz
PFC: IGBT1
PFC: IGBT2
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26
PFC-SPM Current Flow Path
Current Flow @ IGBT Off
Current Flow @ IGBT On
AC
AC(-)
AC(+)
53
PFC-SPM Series
System Connection Diagram
S
R
P
5V
CSC
CFOD
VFO
Control
IC
Fault
IN(S)
IN(R)
IN(S)
IN(R)
15V
Tem p
COM
VCC
C(SC) OUT(WL)
C(FOD)
VFO
IN(WL) OUT(VL)
IN(VL)
IN(UL)
COM(L)
Shunt Resistor
OUT(UL)
VCC
Shunt
Resistor
5V
VTH
RTH
54
N
NSENSE
VAC-
Temperature
Monitoring
27
PFC module line up
Rating
(Motor
rating)
SPM Series
PFC-SPM
44 mm x 26.8 mm
Features
Main
Applications
PSCM
220 Vac
11 Arms
Partial Switching Converter Module
- Built-in LVIC with UVP, OCP
- Built-in thermistor
Air
conditioners
(1 ~ 3 kW)
PFCM*
220 Vac
30 Arms
Power Factor Correction Module
- Built-in LVIC with UVP, OCP
- Built-in thermistor and shunt resistor
Air
conditioners
(3 ~ 5 kW)
*In development
55
Motion-SPM (Smart Power Modules)
for Motor Applications
SPM Series
Rating
(Motor
rating)
DIP
600 V 10~70*A
(0.8 ~ 7.0 kW)
Air conditioners
Washing machines
Treadmills
Industrial inverters
600 V 3~30A
(0.3 ~ 3.0 kW)
3-phase IGBT inverter with
• 3 divided N-terminal for current sensing
• Built-in HVIC with UVP
• Built-in LVIC with UVP, OCP
Air conditioners
Washing machines
Refrigerators
Industrial inverters
500 V 2~3 A
( 50 ~ 100 W)
3-phase FRFET inverter with
• 3 divided N-terminal for current sensing
• Built-in HVIC
• Low EMI & ruggedness
• Small footprint
Fan motors
Water suppliers
Air cleaners
Mini-DIP
44 mm x 26.8 mm
Tiny-DIP
29 mm x 12 mm
Main
Applications
3-phase IGBT inverter with
• 3 divided N-terminal for current sensing
• Built-in HVIC with UVP
• Built-in LVIC with UVP, OCP
• Sense IGBT for low-side
• Built-in thermistor
60 mm x 31 mm
Motion-SPM
Features
*In development
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Related Links
The pdf version of the Power Seminar presentations are available on the our external
website. To access or download the pdfs, please visit
www.fairchildsemi.com/power/pwrsem2006.html
For product datasheets, please visit www.fairchildsemi.com
For application notes, please visit www.fairchildsemi.com/apnotes
For application block diagrams, please visit www.fairchildsemi.com/markets
For design tools, please visit the design center at www.fairchildsemi.com
For more information on SPMTM, please visit www.fairchildsemi.com/SPM
To access FET bench, please visit http://www.transim.com/fairchild/index.html
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