Journal of Power Electronics, Vol. 15, No. 1, pp. 31-38, January 2015
31
http://dx.doi.org/10.6113/JPE.2015.15.1.31
ISSN(Print): 1598-2092 / ISSN(Online): 2093-4718
JPE 15-1-4
A Buck-Boost Type Charger with a Switched
Capacitor Circuit
Jinn-Chang Wu†, Hurng-Liahng Jou*, and Jie-Hao Tsai**
†**
Dept. of Microelectronics Engineering, National Kaohsiung Marine University, Kaohsiung, Taiwan
Dept. of Electrical Engineering, National Kaohsiung University of Applied Sciences, Kaohsiung, Taiwan
*
Abstract
In this paper, a buck-boost type battery charger is developed for charging battery set with a lower voltage. This battery charger
is configured by a rectifier circuit, an integrated boost/buck power converter and a switched capacitors circuit. A boost power
converter and a buck power converter sharing a common power electronic switch are integrated to form the integrated boost/buck
power converter. By controlling the common power electronic switch, the battery charger performs a hybrid
constant-current/constant-voltage charging method and gets a high input power factor. Accordingly, both the power circuit and
the control circuit of the developed battery charger are simplified. The switched capacitors circuit is applied to be the output of
the boost converter and the input of the buck converter. The switched capacitors circuit can change its voltage according to the
utility voltage so as to reduce the step-up voltage gain of the boost converter when the utility voltage is small. Hence, the power
efficiency of a buck-boost type battery charger can be improved. Moreover, the step-down voltage gain of the buck power
converter is reduced to increase the controllable range of the duty ratio for the common power electronic switch. A prototype is
developed and tested to verify the performance of the proposed battery charger.
Key words: Active damping, DFT, LCL filter, Resonance, Wind power system
I.
INTRODUCTION
Portable electronic products and electric bikes have
become more popular due to the progress of the battery
industry in recent years. The performance of batteries
significantly affects the operation of portable electronic
products and electric bikes. The performance and lifetime of
a battery is affected by the battery charger. Therefore, the
operation of a battery depends on a battery charger with good
controllability.
Battery chargers for portable electronic products and
electric bikes require a power source with a low DC voltage.
However, distribution power systems supply a high AC
voltage. Therefore, a battery charger acts as an interface
between a distribution power system and the battery set.
Conventionally, a diode rectifier with a filter capacitor is
Manuscript received Feb. 12, 2014; accepted Aug. 21, 2014
Recommended for publication by Associate Editor Joung-Hu Park.
†
Corresponding Author: jinnwu@mail.nkmu.edu.tw
Tel: +886-7-3917141, Fax: +886-7-3645589, NKMU
*
Dept. of Electrical Eng., Nat’l Kaohsiung Univ. of Applied Sci., Taiwan
**
Dept. of Microelectronics Eng., Nat’l Kaohsiung Marine Univ., Taiwan
applied to convert AC power into DC power for charging a
battery set due to its simple configuration and low cost [1].
Unfortunately, the output voltage of a diode rectifier cannot
be regulated according to the state of charge (SOC) of the
battery set, which will shorten the life of the battery set. In
addition, its input characteristic is nonlinear, resulting in
harmonic current and a poor power factor. The output voltage
of the diode rectifier is about the peak value of the input AC
voltage, and it cannot directly charge the battery set with a
low DC voltage. A low-frequency transformer needs to be
placed at the front of the diode rectifier, which will increase
the volume and weight of the battery charger.
For lowering and regulating the output voltage, a buck
converter can be connected to the diode rectifier in cascade
[2]-[4]. The diode rectifier outputs an absolute voltage of the
utility voltage, and the buck converter converts the absolute
voltage into a regular voltage with a low DC voltage. The
power electronic switch of the buck converter can be
controlled to regulate the output voltage according to the
SOC of the battery set. It also corrects the input current of the
diode rectifier to be approximately sinusoidal. However, the
buck converter cannot work when the absolute voltage is
© 2015 KIPE
32
Journal of Power Electronics, Vol. 15, No. 1, January 2015
lower than the output voltage, and the input current of the
diode rectifier is zero. Hence, the input current will contain a
zero-crossing distortion. In addition, the duty ratio of the
power electronic switch will be small for obtaining a high
step-down voltage gain, and it is difficult to precisely control
the output voltage. To avoid zero-crossing distortion of the
input current, the buck converter can be replaced by a flyback
converter [5], [6] or a buck-boost converter [7], [8]. A
high-frequency transformer is used in the flyback converter to
increase the step-down voltage gain. Although the size of the
high-frequency transformer is small, it will result in an extra
power loss and it will increase the voltage rating of the power
electronic switch. The power factor corrector, which is
configured by a diode rectifier and a boost converter, can
solve the problem of zero-crossing distortion [9]-[14]. The
input current will be sinusoidal and in phase with the input
AC voltage to achieve a unity power factor. However, the
output voltage will be higher than the peak value of the input
AC voltage, and it cannot directly charge the low-voltage
battery set. An extra buck converter or a flyback converter,
which achieves a high step-down gain, needs to be connected
to the output of the power factor corrector for generating a
low DC voltage. This is a two-stage AC-DC power converter
and it complicates both the power circuit and the control
circuit. In addition, the step-up voltage gain for the power
factor corrector is very high when the amplitude of the utility
voltage is low. Considering the parasitic resistor of the
inductor and ignoring the power loss of the power
semiconductor devices, the power efficiency of a boost power
converter can be derived as:
z=
1
1 + rL / R (1 - D b ) 2
(1)
where rL and R are the parasitic resistor of the inductor and
the equivalent load resistor, and Db is the duty of the power
electronic switch [1]. As seen in (1), the efficiency of the
boost converter is evidently degraded under a high step-up
voltage gain. Hence, the efficiency of the boost converter is
very low for the duration of low utility voltage. Since the
valley-fill circuit performs the series-charging and
parallel-discharging of the capacitors, it can be used in the
AC-DC power converter to reduce the required capacity of
bulky electrolytic capacitors [15]-[17]. However, the step-up
voltage gain for the valley-fill circuit based AC-DC power
converter is very high when the amplitude of the utility
voltage is low. The power efficiency of a boost power
converter has been analyzed in [18]. If the power loss of the
power semiconductor devices is considered, the power
efficiency of the boost power converter will be further
degraded after considering the power loss of the power
semiconductor devices, and it is inversely proportional to the
ratio rL/R under the higher duty of the power electronic
switch [18]. This means that the power efficiency of a boost
power converter with a higher duty will be significantly
Fig. 1. Circuit configuration of the proposed buck-boost type
battery charger.
degraded under a light load.
In this paper, a buck-boost type battery charger is
developed. The developed battery charger is configured by a
rectifier circuit, an integrated boost/buck power converter,
and a switched capacitors circuit. The boost/buck power
converter integrates a boost power converter and a buck
power converter to simplify the power circuit. The switched
capacitors circuit is applied to reduce the step-up voltage gain
of the boost power converter and to increase the step-down
voltage ratio of the buck power converter. As a result, the
efficiency of the buck-boost type battery charger is improved.
II.
CIRCUIT CONFIGURATION
Fig. 1 shows the circuit configuration of the proposed
buck-boost type battery charger. The output current/voltage
can be regulated according to the SOC of the battery set, and
the input current can be controlled to be approximately
sinusoidal and in phase with utility voltage to achieve a high
power factor. As seen in Fig. 1, the proposed buck-boost type
battery charger is composed of a diode rectifier, an integrated
boost/buck power converter, and a switched capacitors circuit.
The diode rectifier converts the utility voltage to an absolute
voltage. To perform the function of power factor correction, a
boost converter needs to be connected to the output of the
diode rectifier. In addition, a buck converter should be
applied to step down the output voltage of the boost converter
to match the voltage of the battery set. In the proposed
buck-boost type battery charger, a boost power converter and
a buck power converter are integrated to form an integrated
boost/buck power converter. As seen in Fig. 1, the boost
converter is configured by inductor L1, diodes D1 and D2,
and power electronic switch S1. For the boost converter, the
input is connected to the output of the diode rectifier and the
output is connected to the switched capacitor circuit.
The buck converter is configured by diode D3, inductor L2
and power electronic switch S1. The input of the buck
converter is connected to the switched capacitor circuit and
its output is used to charge the battery set. Accordingly,
A Buck-Boost Type Charger with a Switched Capacitor Circuit
power electronic switch S1 is used in the boost converter and
the buck converter simultaneously. The switched capacitor
circuit is configured by power electronic switch S2,
capacitors C1 and C2, and diodes D4 and D5. The switched
capacitor circuit is similar to a valley-fill circuit. However,
the power electronic switch of the switched capacitor circuit
replaces the diode of the valley-fill circuit. Accordingly,
capacitors C1 and C2 can be operated as individual capacitor
charging, series charging two capacitors or parallel
discharging two capacitors, depending on the states of power
electronic switches S1 and S2 and the amplitude of the utility
voltage. This is different from the valley-fill circuit where the
two capacitors can only be charged in series.
III.
OPERATION PRINCIPLE
A. Switched Capacitor Circuit
In a conventional power factor corrector, the utility voltage
is converted to an absolute voltage by a diode rectifier, and
then a boost converter is used to control the waveform of the
input current and to regulate the output DC voltage. For
nominal operation, the output DC voltage needs to be higher
than the peak value of the utility voltage. For a small-capacity
power factor corrector, the boost converter is generally
operated in the discontinuous conduction mode (DCM) to
reduce the size of the inductor and to achieve zero current
switching. However, the operation of the DCM for a boost
converter will increase the output DC voltage to further
increase the voltage gain. Unfortunately, the higher the
voltage gain of a boost converter is, the lower its power
efficiency will be [1]. In particular, the voltage gain is very
high when the amplitude of the utility voltage is low for
applying the boost converter in the power factor corrector.
Accordingly, the power efficiency of the power factor
corrector is degraded.
For decreasing the voltage gain of the boost converter
under a low amplitude utility voltage, the output of the boost
converter is connected to the switched capacitor circuit in the
proposed buck-boost type charger. Power electronic switch S2
is used in the switched capacitor circuit, which is different
from a valley-fill circuit. When the absolute voltage of the
utility voltage is smaller than half of its peak voltage, S2 is in
the on-state. At this time, only capacitor C1 of the switched
capacitor circuit is connected to the output of the boost
converter. Accordingly, the output voltage of the boost
converter is equal to capacitor voltage VC1. Since capacitors
C1 and C2 discharge power to the buck converter in parallel,
their voltages will be balanced automatically. This means that
capacitor voltage VC1 is about half of the DC output voltage
for a conventional power factor corrector. This is different
from the valley-fill circuit based AC-DC power converter,
where the output voltage is still two times the individual
capacitor voltage. Therefore, the voltage gain of the boost
33
Fig. 2. Conducting path of integrated boost/buck power converter
when S1 is in the on-state.
converter in the integrated boost/buck power converter is half
that of a conventional power factor corrector and the
valley-fill circuit based AC-DC power converter when the
amplitude of the utility voltage is smaller than half of its peak
voltage. As a result, the power efficiency is improved. When
the amplitude of the utility voltage is higher than half of its
peak voltage, S2 is in the off-state. Capacitors C1 and C2 are
connected in series through D4 and then connected to the
output of the boost converter. At this time, the output voltage
of the boost converter in the integrated boost/buck power
converter is similar to that of a conventional power factor
corrector and the valley-fill circuit based AC-DC power
converter. From the above, the output voltage of the boost
converter in the integrated boost/buck power converter can be
divided into two levels by controlling the state of S2 in the
switched capacitor circuit. As a result, the power efficiency of
the buck-boost type battery charger will be improved.
B. Integrated Boost/Buck Power Converter
The integrated boost/buck power converter is composed of
a boost converter and a buck converter sharing a power
electronic switch S1. Fig. 2 shows the conducting path of the
integrated boost/buck power converter when S1 is in the
on-state. The red line shows the conducting path for the boost
converter. The current of inductor L1 of the boost converter
can be represented as:
diL1 vs
=
(2)
L1
dt
where vs is the utility voltage. The current of inductor L1 will
increase to store energy from the utility voltage. The blue line
shows the conducting path of the buck converter. Capacitors
C1 and C2 are connected in parallel through the parallel diode
of S2 and D5. Then they supply power to the buck converter.
The current of inductor L2 of the buck converter can be
represented as:
diL 2 ( Vc - Vo )
(3)
=
L2
dt
where Vc is the higher voltage among C1 or C2, and Vo is the
output voltage. Since C1 and C2 are discharged in parallel, the
34
Journal of Power Electronics, Vol. 15, No. 1, January 2015
(a)
power to the buck converter in parallel. It can also be seen
that the input voltage of the buck converter in the integrated
boost/buck power converter will be half of the output voltage
of the conventional power factor corrector. Hence, the
integrated boost/buck power converter can increase the
step-down voltage ratio when compared with topologies
where the boost converter and the buck converter are
connected in cascade. Therefore, the duty ratio of the buck
converter in the integrated boost/buck power converter can be
extended when compared to that connected to the output of
the conventional power factor corrector. In addition, the
difficulty in precisely controlling the output voltage can be
alleviated.
The boost converter of the integrated boost/buck power
converter is operated in the DCM. The variation of iL1 under
the on-duration of S1 can be represented as:
DI L1,on =
vs DT
(7)
L1
where D is the duty of S1, and T is the switching period. The
variation of iL1 under the off-duration of S1 can be represented
as:
(b)
Fig. 3. Conducting path of integrated boost/buck power converter
when S1 is in the off-state. (a) S2 is in the off-state. (b) S2 is in
the on-state.
capacitor with the higher voltage will discharge more power.
Accordingly, the voltages of C1 and C2 will be balanced. The
current of inductor L2 will increase to store energy from the
switched capacitor circuit.
Fig. 3 shows the conducting path of the integrated
boost/buck power converter when S1 is in the off-state. The
integrated boost/buck power converter contains two
conducting paths, depending on the state of S2. As seen in Fig.
3(a), the energy stored in L1 of the boost converter will
charge C1 and C2 in series through D1 when S2 is in the
off-state, and the current of L1 can be represented as:
di L1 v s - ( Vc1 + Vc 2 )
=
(4)
L1
dt
where VC1 and VC2 are the voltages of C1 and C2, respectively.
As seen in Fig. 3(b), when S2 is in the on-state, the energy
stored in L1 only charges C1, and the current of L1 can be
represented as:
diL1 vs - Vc1
=
(5)
L1
dt
The current of inductor L1 decreases to release its energy.
The energy stored in L2 of the buck converter will charge
output capacitor Cout through D2 regardless of the state of S2,
and the current of L2 can be represented as:
diL 2 - Vo
(6)
=
L2
dt
The current of L2 will decrease.
From the above, it can be seen that both C1 and C2 supply
DI L1,off =
( vs - Vx )t fall
L1
(8)
where Vx may be VC or VC1+VC2 depending on the state of S2,
and tfall is the falling time of iL1. The boost converter is
operated in the discontinuous conduction mode, and:
(9)
DI L1,on = DI L1,off
From (6)-(8), tfall can be derived and represented as:
t fall =
vs
Vx - vs
DT
(10)
tfall should be smaller than the off time (1-D)T of S1. By
combining (6) and (7), the average current of L1 can be
derived as:
iL1,avg =
vs
1
( DT + t fall )
DT
2
L1
(11)
Substituting (9) into (10), the average current of L1 can be
rewritten as:
vs 2 2
Vx
1
(12)
iL1,avg = (
)
D T
2 Vx - vs L1
Since power electronic switch S1 is shared by the boost
converter and the buck converter in the integrated boost/buck
power converter, the duty D can be used to control only one
object. In the buck-boost type charger, the control object can
be either the input current of the boost converter or the output
current/voltage of the buck converter. As can be seen in (12),
the average current of L1 is not directly proportional to the
absolute value of the utility voltage. This means that the input
current of the buck-boost type battery charger will be
distorted if the duty ratio of S1 is fixed. For obtaining a unity
power factor, the control object of the buck-boost type battery
charger is the input current of the boost converter. The input
35
A Buck-Boost Type Charger with a Switched Capacitor Circuit
current of the boost converter needs to be proportional to the
utility voltage, and it can be represented as:
vs 2 2
Vx
1
(
)
D T = k vs
2 Vx - vs L1
(13)
where k is a constant, which determines the input power of
the buck-boost type charger. Accordingly, from the point of
view of the utility voltage, the buck-boost type battery
charger can be operated as a resistor 1/k. From (13), the duty
of S1 can be derived as:
D=
2L1k
T
2
= k' 1 -
(1-
vs
Vx
)
(14)
(a)
(b)
Fig. 4. Simulation results of the buck-boost type charger when
the control object is the input current. (a) Input current. (b)
Charging current.
vs
Vx
where:
k' =
2L1k
(15)
T2
If the duty of S1 can be controlled to follow (14), the
buck-boost type charger can be operated as a resistor to
achieve a unity power factor. The real power injected into the
buck-boost type charger can be regulated by k’ to control the
charging power of the battery set. The buck converter of the
integrated boost/buck power converter is operated in the
continuous conduction mode. Pulse-width modulation
(PWM) is used to control S1. The voltage across diode D3 is a
pulse voltage with an amplitude of VC1, and its average
voltage VD3 can be represented as:
(16)
VD3 = DVC1
The output voltage of the buck converter is the average
voltage VD3 because L2 and Cout are operated as a second
low-pass filter. Since the battery set can be regarded as a
voltage source with a small internal resistor, the output
voltage of (16) will result in a large ripple integrated into the
charging current of the battery set.
For achieving constant-current/constant-voltage charging
of the battery set, the control object of the buck-boost type
battery charger is the output current/voltage of the buck
converter. If the ripple voltage of the switched capacitors
circuit is ignored, the duty D is almost constant. The average
current of L1is shown as (12), and it results in a distortion in
the input current of the buck-boost type charger.
Figs. 4 and 5 show simulation results of the buck-boost
type charger. The parameters of the buck-boost type charger
are shown in Table I. Fig. 4 shows the input current and
charging current of the buck-boost type charger when the
control object is the input current of the boost converter. As
seen in Fig. 4(a), the input current of the buck-boost type
charger is sinusoidal. However, the charging current of the
battery set, shown in Fig. 4(b), contains a large ripple. Fig. 5
shows the input current and charging current of the
buck-boost type charger when the control object is the output
(a)
(b)
(c)
Fig. 5. Simulation results of the buck-boost type charger when
the control object is the charging current. (a) Input current. (b)
Spectrum of input current. (c) Charging current.
current of the buck converter. As seen in Fig. 5(a), the input
current of the buck-boost type charger is slightly distorted.
The spectrum of the input current is shown in Fig. 5(b). The
total harmonic distortion (THD%) of the input current is
about 17%. The ripple of the charging current of the battery
set, shown in Fig. 5(c), is small.
When compared with the conventional two-stage AC-DC
power converter, the proposed buck-boost type battery
charger integrates a boost power converter and a buck power
converter to simplify both the power circuit and the control
circuit. Since the control of the boost power converter and the
buck power converter is integrated, the response of the
proposed buck-boost type battery charger is superior to that
of the conventional two-stage AC-DC power converter where
the control is separated. In addition, the problems of the high
voltage gain under the low amplitude of utility voltage for the
boost power converter, the small duty for the high step-down
voltage gain for the buck power converter and the bulky
electrolytic capacitor are improved in the proposed
buck-boost type battery charger. Although the valley-fill
circuit based AC-DC power converter can solve the problems
of the small duty of the high step-down voltage gain for the
buck power converter and the bulky electrolytic capacitor
36
Journal of Power Electronics, Vol. 15, No. 1, January 2015
[15]-[17], the problem of the high voltage gain under the low
amplitude of utility voltage for the boost power converter
cannot be solved. When compared with the buck converter
based AC-DC power converter [2]-[4], the power circuit is
complicated and the power efficiency is degraded for the
proposed buck-boost type battery charger. However, the
serious problem of zero-crossing distortion, which results in a
high distortion of the input current, is solved in the proposed
buck-boost type battery charger.
IV.
Fig. 6. Control block of the buck-boost type charger.
CONTROL BLOCK DIAGRAM
For considering the charging performance, the control
object of the buck-boost type battery charger is the output
current/voltage of the buck converter. Fig. 6 shows a control
block diagram of the proposed buck-boost type charger. The
hybrid constant-current/constant-voltage charging method is
applied to charge the battery set. If the voltage of the battery
set is lower than the preset voltage, the battery charger
charges the battery set with a constant current. On the other
hand, the battery charger charges the battery set at a constant
voltage when the voltage of the battery set is higher than the
preset voltage. The voltage and current of the battery set are
detected by a voltage sensor and a current sensor. The
detected voltage and current of the battery set are sent to the
inputs of the controllable switch. The position of the
controllable switch depends on which charging mode of the
battery set is selected. The output of the controllable switch is
sent a comparator to compare it with a setting value, and the
compared result is sent to the PI controller. For simplifying
the controller, the gains of the voltage sensor and the current
sensor are adjusted so as to unify the setting value for the
constant voltage charging and constant current charging of
the battery set. Since the change for the voltage and current of
the battery set is slow, the parameters of the PI controller are
not critical. The output of the PI controller is sent to the
PWM circuit to obtain the control signal of S1. The utility
voltage is detected by a voltage sensor and sent to the
absolute circuit. The absolute utility voltage is sent to a
comparator to be compared with Vs/2, which is half the
amplitude of the utility voltage. The output of the comparator
is the control signal of S2.
The PI controller can be represented as:
G c (s) =
k p s + ki
s
(17)
The duty of S1 can be represented as:
v
D= m
Vtri
(18)
where vm is the modulation signal, and Vtri is the amplitude of
the carrier signal for the PWM circuit. Referring to (16)-(18),
the model of the buck converter operated under charging by a
constant-current, is shown in Fig. 7. In Fig. 7, kcur is the gain
Fig. 7. Model of buck converter.
of the current sensor and RL is the stray resistor of L2. kcon is
the gain of the buck converter and it can be represented as:
V
k con = c1
Vtri
(19)
V. EXPERIMENTAL RESULTS
To verify the performance of the proposed buck-boost type
charger, a prototype, using a DSP TMS320F28035 as a
controller, was developed and tested. The parameters of the
prototype are shown in Table I. The battery set is configured
by connecting two lead-acid batteries in series. The utility
voltage is from a single-phase distribution power system with
a voltage and frequency of 110V and 60Hz, respectively.
Since the change in the voltage and current of the battery set
is slow, the phase margin for the buck-boost type battery
charger is not critical. According to the model of Fig. 7, the
phase margin for the buck converter is about 90o under
charging by a constant-current.
Fig. 8 shows the experimental results of the input
characteristic for the proposed buck-boost type charger. As
seen in Fig. 8(a), the input current is approximately
sinusoidal and in phase with the utility voltage. The power
factor is 0.93. As seen in Fig. 8(b), the THD% of the input
current is 16.6%. However, the major harmonic components
are within the standard limits of IEC 6100-3-2 Class C. Fig. 9
shows the experimental results for the voltages of the devices
in the proposed buck-boost type charger. As seen in Fig. 9(b),
the voltage across the switched capacitor circuit is switched
between the voltages of capacitors C1 and C2 connected in
series and in parallel. When the absolute voltage of the utility
voltage is smaller than half of its peak voltage, S2 is in the
on-state and the voltage across the switched capacitor circuit
is equal to the capacitor voltage VC1, regardless of the
37
A Buck-Boost Type Charger with a Switched Capacitor Circuit
TABLE I
MAINS PARAMETERS OF THE PROTOTYPE
Filter
1mH, 1mF
Switching
frequency
40kHz
Inductor L1
400mH
PI controller
kp:1, ki:100
Inductor L2
DC capacitors
C 1, C 2
DC capacitor
Cout
2mH
820mF
820mF
Fig. 10. Experiment result of the output characteristic for the
proposed buck-boost type charger. (a) Utility voltage. (b)
Charging current. (c) Battery voltage.
TABLE II
POWER EFFICIENCY
Input power
(a)
(b)
Fig. 8. Experimental result of input characteristic for the
proposed buck-boost type charger. (a) Utility voltage and input
current, (b) Spectrum of input current.
Fig. 9. Experimental result for the voltages of the devices in the
proposed buck-boost type charger. (a) Utility voltage. (b) Voltage
of switched capacitor circuit. (c) Voltage of S1. (d) Voltage of S2.
switching of S1. However, capacitors C1 and C2 are charged
in series and discharged in parallel according to the switching
operation of S1 while the absolute voltage of the utility
voltage is higher than half of its peak voltage and S2 is in the
off-state. As seen in Fig. 8(c), the voltage of S1 is switched
between the voltage of the switched capacitor circuit and zero
voltage. Hence, the off-state voltage of S1, shown in Fig.9(c),
contains two DC voltage levels, the capacitor voltage VC1 and
the summation of the capacitor voltages VC1 and VC2. Since
the off-state voltage of S1 is reduced when the absolute
voltage of the utility voltage is smaller than half of its peak
36W
44w
56W
71W
81W
charger with valleyfill circuit
88.2%
90%
90.9%
91.2%
90.5%
proposed buck-boost
type charger
90.3%
90.9%
91.6%
92.6%
92%
voltage, the switching loss is also reduced to advance the
power efficiency. Fig. 9(d) shows the voltage of S2. As seen
in Fig. 9(d), S2 is in the on-state and its voltage is zero when
the absolute voltage of the utility voltage is smaller than half
of its peak voltage. When the absolute voltage of the utility
voltage is higher than half of its peak voltage, S2 is in the
off-state. Since the parallel diode of S2 is switching in
complement with S1 when S2 is in the off-state, the off-state
voltage of S2 will be changed between the capacitor voltage
VC1 and zero. Fig. 10 shows the charging current of the
battery set. As seen in Fig. 10(b), the ripple for the charging
current of the battery set is small to protect the battery set.
The power efficiency of the proposed buck-boost type
charger and the charger with a valley-fill circuit (S2 of the
switched capacitor circuit is still turned off) is shown in Table
II. The input power is measured by a power quality
analyzer (FLUKE 43B) and the output power is measured by
a digital storage oscilloscope (Tektronix TPS 2024). As seen
in Table II, the power efficiency is improved by the switched
capacitor circuit of the proposed buck-boost type charger.
VI. CONCLUSION
Due to the popularization of portable electronic products
and electric bikes, a low voltage charger is necessary.
Therefore, a buck-boost type charger is proposed in this paper.
The proposed buck-boost type charger is composed of an
integrated boost/buck power converter and a switched
capacitor circuit. A boost converter and a buck converter
sharing a power electronic switch are integrated to be a
boost/buck power converter to simplify the power circuit.
The salient feature is that the switched capacitors circuit can
38
Journal of Power Electronics, Vol. 15, No. 1, January 2015
control the DC link voltage with two DC voltage levels. The
switched capacitor circuit can change the output voltage of
the boost converter according to the utility voltage to advance
the power efficiency and reduce the input voltage of the buck
converter to increase the step-down voltage ratio. From the
experimental results, it can be seen that the proposed
buck-boost type charger can achieve a unity power factor,
output a regular DC voltage, and charge the battery set.
REFERENCES
[1] D. W. Hart, Introduction to Power Electronics, Prentice
Hall, 2004.
[2] V. F. Pires and J F. Silva, “Single-stage double-buck
topologies with high power factor,” Journal of Power
Electronics, Vol. 11, No. 5, pp. 655-661, Sep. 2011.
[3] X. Xie, C. Zhao, L. Zheng, and S. Liu, “An improved buck
PFC converter with high power factor,” IEEE Trans. Power
Electron., Vol. 28, No.5, pp. 2277-2284, May 2013.
[4] L. Huber, L. Gang, and M. M. Jovanovi´c, “Design-oriented
analysis and performance evaluation of buck PFC front
end,” IEEE Trans. Power Electron., Vol. 25, No. 1, pp.
85-94, Jan. 2010.
[5] S. P. Yang, S. J. Chen, and J. L. Lin, “Dynamics analysis
of a low-voltage stress single-stage high-power factor
correction AC/DC flyback converter,” IET Power
Electronics, Vol. 5, No. 9, pp. 1624-1633, Sep. 2012.
[6] J. Zhang, D. D.-C. Lu, and T. Sun, “Flyback-based
single-stage
power-factor-correction
scheme
with
time-multiplexing control,” IEEE Trans. Ind. Electron., Vol.
57, No. 3, pp. 1041-1049, Mar. 2010.
[7] J. Chen, D. Maksimovic, and R. W. Erickson, “Analysis and
design of a low-stress buck-boost converter in
universal-input PFC applications,” IEEE Trans. Power
Electron., Vol. 21, No. 2, pp. 320-329, Feb. 2006.
[8] A. Abramovitz and K. M. Smedley, “Analysis and design of
a tapped-inductor buck–boost PFC rectifier with low bus
voltage,” IEEE Trans. Power Electron., Vol. 26, No. 9, pp.
2637-2649, Sep. 2011.
[9] E. L. Huber, B. T. Irving, and M. M. Jovanovic, “Effect of
valley switching and switching-frequency limitation on
line-current distortions of DCM/CCM boundary boost PFC
converters,” IEEE Trans. Power Electron., Vol. 24, No. 2,
pp. 3390347, Feb. 2009.
[10] Y. Fei, R. Xinbo, Y. Yang, and Y. Zhihong, “Interleaved
critical current mode boost PFC converter with coupled
inductor,” IEEE Trans. Power Electron., Vol. 26, No. 9, pp.
2404-2413, Sep. 2011.
[11] J. W. Shin, B. C. Hyeon, and B. H. Cho “Digital control of
a power factor correction boost rectifier using diode current
sensing technique,” Journal of Power Electronics, Vol. 9,
No. 6, pp. 903-910, Nov. 2009.
[12] M. Pahlevaninezhad, P. Das, J. Drobnik, and P. K.Jain, ”A
ZVS interleaved boost AC/DC converter used in plug-in
electric vehicles,” IEEE Trans. Power Electron., Vol. 27,
No. 8, pp. 3513-3529, Aug. 2012.
[13] H. S. Athab and D. D.-C Lu, “Simple controller for
single-phase power factor correction rectifier,” IET Power
Electron., Vol. 3, No.4, pp. 590-600, Apr. 2010.
[14] N. Genc and I. Iskender, “DSP-based current sharing of
average current controlled two-cell interleaved boost power
[15]
[16]
[17]
[18]
factor correction converter,” IET Power Electron., Vol. 4,
No .9, pp. 1015-1022, Sep. 2011.
H. Ma, C. Zheng, W. Yu, B. Gu, J. S. Lai, and Q. Feng,
“Bridgeless electrolytic capacitor-less valley-fill AC/DC
converter for offline twin-bus light-emitting diode lighting
application,” IET Power Electron., Vol. 6, No. 6, pp.
1132-1141, Jun. 2013.
J. H. Kim, D. Y. Cho, J. P. Hong, and G. W. Moon,
“Boost integrated flyback AC-DC converter with valley fill
circuit for LED light bulb,” in Proc. IPEMC, Vol. 1, pp.
457-462, 2012.
J. C. W. Lam and P. K. Jain, “A modified valley fill
electronic ballast having a current source resonant inverter
with improved line-current total harmonic distortion (THD),
high power factor, and low lamp crest factor,” IEEE Trans.
Ind. Electron., Vol. 55, No. 3, pp. 1147-1159, Mar. 2008.
I. R. Balasubramanian, S. I. Ganesan, and N. Chilakapati,
“Impact of partial shading on the output power of PV
systems under partial shading conditions,” IET Power
Electron., Vol. 7, No. 3, pp. 657-666, Mar. 2014.
Jinn-Chang Wu was born in Tainan, Taiwan
R.O.C., in 1968. He graduated from the
National Kaohsiung Institute of Technology,
Kaohsiung, Taiwan, in 1988, and received
his M.S. and Ph.D. degrees from the
National Cheng Kung University, Tainan,
Taiwan, in 1992 and 2000, respectively, all
in Electrical Engineering. Since 2007, he has
been an Associate Professor in the Department of
Microelectronic Engineering, National Kaohsiung Marine
University, Kaohsiung, Taiwan. His current research interests
include power electronics and their applications.
Hurng-Liahng Jou was born in Taiwan
R.O.C., in 1959. He received his B.S. degree
in Electrical Engineering from Chung Yuan
University, Jonglih, Taiwan, in 1982, and his
M.S. and Ph.D. degrees in Electrical
Engineering from the National Cheng Kung
University, Tainan, Taiwan, in 1984 and
1991, respectively. He is currently a
Professor in the Department of Electrical Engineering of the
National Kaohsiung University of Applied Sciences, Kaohsiung,
Taiwan. His current research interests include power electronics
applications and power quality improvement techniques.
Jie-Hao Tsai was born in Kaohsiung,
Taiwan R.O.C., in 1990. He received his
B.S. degree in Microelectronic Engineering
from the National Kaohsiung Marine
University, Kaohsiung, Taiwan, in 2013. He
is presently working toward his M.S. degree
in Microelectronic Engineering at the
National Kaohsiung Marine University.