Universidad Politécnica de Catalunya
Pontificia Universidad Católica del Perú
Centre Tecnologic de Telecomunicacions de Catalunya
Study of the efficiency of rectifying antenna systems
for electromagnetic energy harvesting
by
Omar André Campana Escala
A thesis submitted in partial fulfillment for the degree of Engineer
in the
Escola Tècnica Superior d‟Enginyeria de Telecomunicació de Barcelona
Department de Teoría de Senyal i Comunicacions
October 2010
Abstract
The focus of this work is on wireless power transfer via electromagnetic radiation. An
RF energy harvesting device consists of three primary subsystems. The first subsystem
is the receiving antenna, which is responsible for capturing all of the RF energy that will
later be used to power the integrated embedded system. The second main subsystem is
the rectification circuitry, which efficiently converts the input RF power into DC output
power. The third subsystem is a DC/DC converter (regulator), which is responsible for
maintaining a constant output DC voltage suitable to power the electronic circuitry
following the harvester for a wide range of input DC voltage variation. Each one of
these three subsystems is integral to the operation of the entire harvester system. A 2.45
GHz electromagnetic energy harvester is proposed. The presented work consists of a)
design and characterization of a circularly polarized aperture coupled patch antenna, b)
performance study, optimization and prototype characterization of various diode
rectifier circuits and c) design and implementation of an evaluation board for a
commercial DC voltage regulator.
ii
Acknowledgments
Primero quisiera referirme a mis padres porque siempre me mostraron todo su apoyo y
preocupación por todo lo que hacía, en lo buenos y malos momentos que pude haber
pasado estuvieron allí conmigo. El tiempo que pase alejado de ellos solo ha hecho que
los valore aún más, sin duda son ustedes los que merecen toda mi gratitud.
A los amigos y profesores que pude conocer gracias a lo largo de mi carrera de
Telecomunicaciones, tanto en la Pontificia Universidad Católica del Perú como en la
Universidad Politécnica de Catalunya, pero sobre todo a aquellos compañeros con los
que tuve la oportunidad de viajar a Barcelona: Jesús, Renzo, Oscar, Bruce, Javier,
César, Ronaldo, Gustavo, Gianfranco, Hugo y Jonathan. Fue muy importante el estar
unidos en un lugar que era nuevo para nosotros. Muchas gracias por todo. Quisiera
agradecer de manera especial a Nuttsy, una persona que es más que una amiga para mí,
quien me manifestó todo su apoyo en todo momento a pesar de la distancia.
Gracias Apostolos, mi director de proyecto, por toda la ayuda brindada durante la
realización de este trabajo, he aprendido mucho durante la investigación y ha sido muy
gratificante; gracias también a Selva Via y Ana Collado
incondicional apoyo durante la implementación del proyecto.
iii
por mostrarme su
Contents
Abstract
ii
Acknowledgments
iii
List of Figures
vi
List of Tables
viii
1. Introduction
1
1.1 General View
2. Background
3
5
2.1 The early history of power transmission by radio waves
5
2.2 The modern history of free-space power transmission
7
2.3 Survey of Existing Markets and Research
10
2.4 Previous Works with Rectenna
11
2.5 Electromagnetic Environment
12
3. Antenna
14
3.1 Verification of the Agilent ADS
3.1.1 Momentum Simulation
14
3.1.2 LineCalc Tool
15
3.2 Antenna Design
iv
14
15
3.2.1
Circularly Polarized Antenna
15
3.2.2
Design Process
18
3.2.3
Antenna Measurements
21
4. Rectifier
28
4.1 Harmonic Balance
28
4.2 Impedance Matching Tool
28
4.3 Voltage multiplier
29
4.4 Rectifier design and optimization
30
4.5 Measurements
36
5. Regulator
41
5.1 TPS6120x device
41
5.2 Design Process
42
6. Conclusions and Future work
46
Bibliography
47
v
List of Figures
1.1
Relative improvements in laptop computing technology from 1990–2003
1.2
Complete block diagram
2.1
Nikola Tesla in his Colorado Springs Laboratory which was constructed to
experiment with radio waves for power transmission
2.2
MPT demonstration to helicopter with W.C. Brown
2.3
MPT Laboratory Experiment in 1975 by W.C. Brown
2.4
First Ground-to-Ground MPT Experiment in 1975 at the Venus Site of JPL
Goldstone facility
2.5
Schematic of a rectenna and associated power management circuit
2.6
Diagram of various microwave power sources and their typical density levels
3.1
LineCalc tool
3.2
Illustration of Elliptical Polarization
3.3
CP antenna. Side View
3.4
CP antenna. Top View
3.5
Substrate
3.6
Antenna Layout
3.7
Antenna
3.8
S11 parameter
3.9
Measuring the antenna‟s S11 parameter with VNA
3.10
Comparison
3.11
Antenna 3D Radiation pattern
3.12
Anechoic chamber measurements
3.13
Receiving antenna
3.14
Transmission antenna
3.15
Axial Ratio simulation by ADS
3.16
Measured Axial Ratio at broadside
4.1
Basic matching scheme
4.2
Basic Rectifier
4.3
Voltage Doubler
4.4
Charge Pump Circuit
vi
4.5
Schottky Diode
4.6
Half-wave rectifier
4.7
Full-wave rectifier
4.8
Diode and Capacitor equivalent circuits
4.9
Comparison between different rectifier orders
4.10
Comparison between different rectifiers based on Vout
4.11
Comparison between order 1 and order 2 based on efficiency
4.12
Comparison between order 1 and order 2 based on output voltage
4.13
Rectifier prototypes
4.14
One-diode rectifier S11 parameter
4.15
Two-diode rectifier S11 parameter
4.16
One-diode rectifier Output Voltage vs. Input Power
4.17
Two-diode rectifier Output Voltage vs. Input Power
4.18
One-diode rectifier Output Voltage from 2.3 GHz. to 2.6 GHz. with -20 dBm
Input Power
4.19
Two-diode rectifier Output Voltage from 2.3 GHz. to 2.6 GHz. with -20 dBm
Input Power
4.20
One-diode rectifier output Voltage from 2.3 GHz. to 2.6 GHz. with -10 dBm.
4.21
Two-diode rectifier output Voltage from 2.3 GHz. to 2.6 GHz. with -10 dBm.
5.1
Regulator Schematic
5.2
Regulator Circuit Layout Top view
5.3
Regulator Circuit Layout Bottom View
5.4
Regulator Circuit Top View
5.5
Regulator Circuit Bottom View
vii
List of Tables
2.1
Chronology of wireless power transmission demonstration and experiments
3.1
Substrate parameters utilized
3.2
Dimensions of the antenna
4.1
Villard Voltage Doubler Order 1
4.2
Villard Voltage Doubler Order 2
4.3
Optimized values for the Villard Voltage Doubler Order 1
4.4
Optimized values for the Villard Voltage Doubler Order 2
4.5
Final Values for the order one rectifier
4.6
Final Values for the two-diode rectifier
4.7
Efficiency
5.1
Recommended operating conditions
5.2
Regulator Components
viii
Chapter 1
Introduction
Power, when talking about wireless communications, is a feature that is really important
to take into account because of the influence it has on the autonomy, weight and size of
portable devices. Therefore, energy harvesting techniques have been proposed to try to
give solution to this problem: we can have a variety of alternative energy sources that
are less harmful to the environment. This kind of environmental friendly energy sources
include energy harvesting from rectennas, passive human power, wind energy and solar
power. Power we can extract from those techniques is limited by regulations and freespace path loss. As a general idea, small dimensions are a basic feature of portable
devices, so the rectenna should be the same way. Since we are talking about small sizes,
the received power will be low. As a conclusion, we can say that wireless power
transfer is better suitable for low-power applications, e.g., a low-power wireless sensor.
The way technology advance every year allow the decrease of certain characteristics in
digital systems, like size and power consumption, that will lead to the gain of new ways
of computing and use of electronics, as an example we have wearable devices and
wireless sensor networks. Currently, these devices are powered by batteries, however,
they present many disadvantages such as: the need to either replace them or recharge
them periodically and their big size and weight compared to high technology
electronics. A solution proposed to this problem was stated before: to extract (harvest)
energy from the environment to either recharge a battery, or even to directly power the
electronic device. Fig.1.1 shows the improvements in technology comparing batteries
with other devices.
1
Fig. 1.1 [1].
Harvesting wireless power techniques are mostly based on radio-frequency
identification, or RFID. Basically, the transmission part sends RF signals that carries
information to a chip to convert it to DC electricity to power the application. Then, a tag
composed by an antenna and a microchip responds by sending back data about the
object it is attached to.
In order to be able to transfer power wirelessly an efficient rectenna is needed.
Therefore, we present a rectenna design modeled with numerical analysis and harmonic
balance simulation. This provides a good insight in the effect of the several parameters
on the performance of the rectenna.
RF
Antenna
AC
0.4V
Rectifier
3.3V
Regulator
Fig. 1.2 Complete system block diagram.
In Fig. 1.2 we can see how our system works: First, the antenna (a circularly polarized
antenna) is in charge of capturing all the RF signals; then the rectifier circuit will
“extract” the power from those signals and convert it in DC voltage efficiently. Finally
2
there is a regulator circuit capable of working with low input voltages which is desirable
for this kind of project.
Several operating frequencies for the rectenna have been investigated in the literature.
Traditionally the 2.45 GHz Industrial Scientific and Medical (ISM) band has been
utilized due to the presence of Wi-Fi networks; additionally the 5.8 GHz ISM band has
also been considered which implies a smaller antenna aperture area than that of 2.45
GHz. Both frequency bands present similar advantages because they have comparably
low atmospheric loss, cheap components availability, and high conversion efficiency.
The frequency bands corresponding to mobile telephone systems such as 800 MHz, 900
MHz and 1800MHz also present good alternatives for electromagnetic energy
harvesting systems, although they require a larger antenna size.
A starting point is to ask ourselves if there is an efficient way to power active devices.
Along the previous years, there have been some methods proposed and implemented:
microwave power transmission [2, pp 87-89], bio-batteries [3, pp 25-28], RFID [4, pp
1-5], surface acoustic wave devices [5, pp 69-72], piezoelectric generators [6, pp 897904], differential-heat generators [7, pp 5/1-5/6], solar cells [8, pp 1199-1206], and so
on.
This work has two goals: (1) powering of low-power applications and (2) RF energy
recycling. If we consider that the use of batteries has some disadvantages like the
limited life period they have, plus the pollution generated from their disposal, it is very
encouraging to think that if every wireless sensor in the world have the kind of power
source presented in this work, it would be a great progress in the way we try to keep our
planet clean.
1.1 General View
This paper is organized as follows:

Chapter 2 gives some information about previous work done in this area.
3

Chapter 3 describes the design, simulation results, measurements and fabrication
of the antenna.

Chapter 4 describes the design, simulation results, measurement and fabrication
of the rectifier.

Chapter 5 gives information about the last part of the system: Regulator

Chapter 6 presents some conclusions and future work.
4
Chapter 2
Background
2.1 The early history of power transmission by radio waves
Power transmission by radio waves dates back to the early work of Heinrich Hertz
around 1880, who demonstrated the electromagnetic wave propagation in free space
using parabolic reflectors at both ends (transmitting and receiving) of the system. In
these terms, his experiments have many similarities to the work done in the present
years. The prediction and evidence of the radio wave in the end of 19th century was the
start point for wireless power transmission.
Nicola Tesla suggested an idea of wireless power transmission (WPT) and started
working on his first WPT experiment in 1899 [9][10]. He actually built a huge coil
connected to a high mast of 200-ft with a 3 ft-diameter ball at its top. The amount of
power needed to feed the Tesla coil was about 300 kW, it resonated at 150 kHz and the
RF potential at the top sphere reached 100 MV. Unfortunately, he failed because all the
transmitted power was diffused to all directions with 150 kHz radio waves whose wave
length was 21 km. (Fig. 2.1)
5
Fig. 2.1 Nikola Tesla in his Colorado Springs Laboratory which was constructed to experiment with radio
waves for power transmission. [11]
After Tesla‟s experiment, researchers realized that efficient point-to-point transmission
of power depended on concentrating the electromagnetic energy into a narrow beam
[11]. The solution was to use RF signals of shorter wavelengths and to use optical
reflectors. Unfortunately, by the first thirty-five years of the 20th century, those devices
were not available to provide even a few milliwatts of energy at these wavelengths;
neither sufficient power was available for experimental work in communication and
radar systems.
In the 1930s, great advance in generating high-power microwaves, 1-10 GHz radio
waves, was achieved by the invention of the magnetron and the klystron, developed first
in Great Britain. This made huge improvement in radar technology, however there was
no immediate consideration to utilize this technology in power transmission, for this to
play an important role, more than a decade had to pass after World War II.
6
2.2 The modern history of free-space power transmission
The modem history of free-space power transmission is basically about the development
of the technology of microwave power transmission and the experiments related to it.
These ranged from the microwave-powered helicopter, to the solar-power satellite
concept with microwave transmission to Earth. The variety of requirements of these
proposed applications had an influence on the direction technology has taken. For
example, the use of the 2.4–2.5 GHz band (ISM – Industrial, Scientific and Medical),
although was originally used for experimental purposes, it‟s also a frequency where the
efficiencies of the microwave components are very high.
In the late 1950‟s many developments converged to make possible the efficient
transmission of power wirelessly a reasonable concept [12]. A great contribution was
done by Goubau, Schwering, and others that demonstrated that microwave power could
be transmitted with efficiencies approaching 100% by a beam waveguide consisting of
lenses or reflecting mirrors [9][17].
W.C. Brown started in the 1960s the first MPT (Microwave Power Transmission)
research and development based on the technology won during the World War II. He
introduced the term rectenna (rectifying antenna) and developed one. The efficiency of
the first rectenna developed in 1963, working at the 2-3 GHz. band, was 50 % at output
4WDC and 40% at output 7WDC, respectively. With the rectenna, he succeeded in
MPT experiments to wired helicopter in 1964 and to free-flied helicopter in 1968 (Fig.
2.2).
7
Fig. 2.2 MPT demonstration to helicopter with W. C. Brown. [11]
In 1970s, he tried to increase the total efficiency with 2.45 GHz microwave. First, in
1970, overall DC-DC total efficiency was only 26.5 % at 39WDC in Marshall Space
Flight Center. Then, in 1975, DC-DC total efficiency was finally 54 % at 495 WDC
with magnetron in Raytheon Laboratory (Fig. 2.3). In parallel, He and his team
succeeded in the largest MPT demonstration in 1975 at the Venus Site of JPL Goldstone
Facility (Fig. 2.4).
Fig. 2.3 MPT Laboratory Experiment in 1975 by W. Brown. [13]
8
Fig. 2.4 First Ground-to-Ground MPT Experiment in 1975 at the Venus Site of JPL Goldstone
facility. [13]
In the past decade, many useful wireless devices were introduced in the market.
Nevertheless, their main disadvantage is the lack of autonomy they have due to their
inability to work independent of centralized power sources for an infinite duration. As a
result, wireless devices depend on the relatively slow advancements in rechargeable
battery technology.
Table 2.1 gives us a summary of all the events regarding important energy harvesting
experiments and where they took place.
Table 2.1 Chronology of wireless power transmission demonstrations and experiments. [2]
Year
Place
Demonstration
1964
Massachusetts, U.S.A.
Raytheon-Brown
Microwave-powered helicopter
1969
Massachusetts, U.S.A.
Beam-riding microwave
Helicopter (Raytheon-Brown)
1974
Massachusetts, U.S.A.
Raytheon Lab
Demonstration of WPT
Huntsville, Alaska, U.S.A.
NASA Marshall Space Flight Center
demo
1975
JPL-Goldstone DSN site Mojave Desert,
U.S.A.
9
Goldstone Test 30 kW. Over 1 mile
1982
Massachusetts, U.S.A.
Thin film etched-circuit rectenna
achieves 1W/g
1983
Suborbital Launch from Kagoshima,
MINIX Space Plasma Experiment
Japan
1987
Canada
SHARP first public demonstration
flights
1991
Princeton, New Jersey, U.S.A.
Rockwell/Sarnoff Microwave rover
experiments at 5.86 GHz.
1992
Massachusetts, U.S.A.
Brown, Raytheon 2.45 test rig demo in
U.S. in preparation for ISU 92
1992
Kitakyushu, Japan
Brown unit demonstrated on television
in Kitakyushu Japan during ISU, Space
Solar Power Program Design Project
1992
Japan
MILAX Microwave Lifted Aircraft
Experiment
1993
Suborbital Flight launched from
ISY METS (Microwave Energy
Kagoshima, Japan
Transfer in Space) experiment Japan
(ISU-U.S.A. rectenna flown)
1993
Huntsville, Alaska, U.S.A.
Brown 2.45 GHz unit demonstrated at
ISU 93 Summer Session
1993
Binghamton, New York, U.S.A.
Brown 2.45 GHz. Unit demonstrated to
New York State Electric and Gas
Company
1993
Low Earth orbit (near Mir Space Station)
Banner ground illumination experiment
1994
Institute for Space and Astronautical
SPS 2000 scale model demonstration
Sciences near Tokyo, Japan
unit prepared by Nagamoto
Kansai Region (Osaka, Japan)
Kansai Electric ground to ground
1994
demonstration.
2.3 Survey of Existing Markets and Research
Recently significant technological advances have been made towards maximizing the
capability for autonomous operation of wireless devices. For example, recent
advancements in rechargeable batteries and electric double‐layer capacitors, as well as
technologies that harvest solar energy and exploit the piezoelectric effect have been
effective at satisfying a large portion of the established market need.
10
To explain in more detail the issue about the batteries we can say that, rechargeable
battery capacity has been increasing by approximately 6% per year [15] and, as a result,
wireless devices have more time to operate without being re‐energized. However, this is
only a temporary solution to the real problem. That‟s why those products that solely
exploit improvements in battery life still present autonomy restrictions for wireless
applications.
Solar power technology has also become a viable solution for many industrial,
commercial, and military applications. Nonetheless, at the current level of technology,
solar power provides an inadequate solution for many wireless devices, for example: the
solar cell‟s location relative to the sun, time of operation, and weather conditions, as
well as the relatively high price per watt of power and solar cells [15].
One interesting technology, which has been researched recently, has to do with
piezoelectric energy harvesting devices [15]. This technology exploits certain materials‟
ability to induce an electric potential after the application of a mechanical force. For
example, to take advantage of applied pressure to a human kneecap during normal
movement and use this mechanical motion to induce an electric potential. Many
mechanical systems inherently create vibrational motion during operation, and
consequently, this energy could be harvested.
2.4 Previous works with Rectenna
The word “rectenna” is the result of joining “rectifying circuit” and “antenna” and was
invented by W. C. Brown in 1960‟s [9][11]. The rectenna is a passive element with a
diode that can receive and rectify microwave power to DC, therefore it can operate
without any power source. There are many published research works related to rectenna
elements. The antenna can be any type such as dipole[11][17], Yagi-Uda
antenna[24][25], microstrip antenna[26][27], monopole[28], loop antenna[29][24],
coplanar patch[31], spiral antenna[32], or even parabolic antenna[33]. The rectenna can
also take any type of rectifying circuit such as single shunt full-wave
rectifier[34][45][36][37][38][39][40], full-wave bridge rectifier[41][42][43][40], or
other hybrid rectifiers[26]. The circuit, especially the diode, determines the RF-DC
11
conversion efficiency. Silicon Schottky barrier diodes were usually used for the
previous rectennas. New diode devices like SiC and GaN are expected to increase the
efficiency. The rectennas with FET[44] or HEMT[45] appear in recent years. The world
record of the RF-DC conversion efficiency among developed rectennas is
approximately 90% at 4W input of 2.45 GHz microwave [41]. Other rectennas in the
world have approximately 70 – 90 % at 2.45GHz or 5.8GHz microwave input.
Fig. 2.5 Schematic of a rectenna [46]
Fig. 2.6 Diagram of various microwave power sources and their typical power density levels. [47]
2.5 Electromagnetic Environment
There are several distinct scenarios for wireless powering, and the specific design is
highly dependent on the incident waves that carry the energy:

In the case of one or more high-directivity narrowband with Line of Sight
transmitters, fixed polarizations and power level, the efficiency of the rectenna
can be very high.
12

In the case of one or more medium-power and semi-directional transmitters. The
transmitters can be single-frequency, multiple frequency or broadband.

Unknown transmitters over a range of frequencies, power levels, generally
unpolarized, with varying low-level spatial power densities.
The incident power density on the rectenna, S (θ ,φ ,f ,t) , is a function of incident
angles, and can vary over the spectrum and in time. The effective area Aeff (θ, φ, f), will
be different at different frequencies, for different incident polarizations and incident
angles. The average RF power over a range of frequencies at any instant in time is given
by:
1
PRF (t ) 
f high  f low
f high 4
  S ( , , f , t ) A
eff
( ,  , f )ddf
f low 0
Where  is the solid angle in steradians and S (, f , t ) is the time-varying frequency
and angle-dependent incident power density. Aeff is the angle-, frequency-, and
polarization-dependent effective area of the antenna. The DC power for a single
frequency ( fi ) input RF power, is given by:
PDC ( f i )  PRF ( f i ,t ).[ PRF ( f i , t ),  , Z DC ]
where  is the conversion efficiency, and depends on the impedance match  ( PRF , f )
between the antenna and the rectifier circuit, as well as the DC load impedance. The
reflection coefficient in turn is a nonlinear function of power and frequency.
13
Chapter 3
Antenna
3.1 Verification of the Agilent ADS tools
3.1.1 Momentum Simulation
Agilent Momentum is based on the Method-of-Moments (MoM) which is a numerical
method to solve Maxwell‟s equations for planar structures in multilayer dielectric
substrates [57]. The conducting surfaces of a given antenna structure are meshed into
different cells and the currents flowing on them are discretized and expanded in a set of
basic functions according to the mesh structure and subsequently determined
numerically. In addition to simulating antenna structures, this type of simulation is used
to accurately determine the electromagnetic behavior of planar transmission lines and
interconnects. Compared to a circuit simulator such as Agilent S-parameter simulator, it
additionally accounts for radiation, as well as coupling among adjacent circuit
components.
In the simplest case, the basic functions are rectangular approximations to the Dirac
delta function. Because the widths of the rectangular sections are non-zero, only a finite
(reasonably small) number of them are needed to cover the antenna wire structure. The
next more complicated basis functions are triangular in shape. This gives a smoother
approximation to the current distribution, in which the current distribution is piecewiselinear between the matching points. In general, the “n-th moment” is obtained by
integrating the product of the Green‟s function with the n-th basis function.
14
3.1.2 LineCalc Tool
The dimensions of the various transmission lines used in the antenna and rectenna
design were obtained using the tool LineCalc of Agilent ADS. Given the physical
dimensions and material properties, LineCalc accurately computes Z 0 and  r ,e for
microstrip as well as for a large number of other planar waveguides. Conversely, it can
synthesize a land width given the other parameters such as Z 0 , d , t ,  r and frequency.
An example of the graphical interface of LineCalc is shown in Fig. 3.1.
Fig. 3.1 Graphical interface of “LineCalc” tool of Agilent ADS.
3.2 Antenna Design
3.2.1 Circularly Polarized Antenna [54]
The energy radiated by any antenna is contained in a transverse electromagnetic wave
that is comprised of an electric and a magnetic field. These fields are always orthogonal
to one another and orthogonal to the direction of propagation. The electric field of the
electromagnetic wave is used to describe its polarization and hence, the polarization of
the antenna.
15
In general, all electromagnetic waves are elliptically polarized meaning that the total
electric field of the wave is comprised of two linear components, which are orthogonal
to one another and have different magnitude and phase. At any fixed point along the
direction of propagation, the total electric field would trace out an ellipse as a function
of time. This concept is illustrated in Fig. 3.2, where, at any instant in time, Ex is the
component of the electric field in the x-direction and Ey is the component of the electric
field in the y-direction. The total electric field E, is the vector sum of Ex plus Ey.
Keeping Fig. 3.2 in mind, we can define Axial Ratio as the ratio of the magnitude of the
orthogonal components of an E-field. A circularly polarized field is made up of two
orthogonal E-field components of equal amplitude (and 90º out of phase). Because the
components are equal magnitude, the axial ratio is 1 (or 0 dB). The axial ratio for an
ellipse is larger than 1 (>0 dB). The axial ratio for pure linear polarization is infinite,
because the orthogonal component of the field is zero.
Fig. 3.2 Illustration of Elliptical Polarization
Circularly Polarized (CP) antennas have shown great advantages in many areas, but the
main benefit of using CP antennas is that the transmitter and the receiver don‟t have to
be strictly aligned. .A circularly polarized wave radiates energy in the horizontal,
vertical planes as well as every plane in between. If the rotation is clockwise, the sense
is called right-hand-circular (RHC). If the rotation is counterclockwise, the sense is
called left–hand-circular (LHC).
Some of the advantages this kind of polarization can give us are:
16
Reflectivity: Radio signals are reflected or absorbed depending on the material they
come in contact with. Because linear polarized antennas are able to transmit or receive
only in one plane, if the reflected signal is not precisely in the same plane, that signal
will be lost. Since circular polarized antennas send and receive in all planes, the signal
is transferred to a different plane.
Absorption: RF signals from different planes are absorbed differently depending on the
type of material being struck. Because it transmits on all planes, a CP antenna has a
higher probability of penetration to deliver a successful, stable link.
Phasing Issues: High-frequency systems (i.e. 2.4 GHz and higher) that use linear
polarization typically require a clear line of sight path so they can avoid obstructions
that may generate reflected signals, which weaken the propagating signal. Reflected
linear signals return to the propagating antenna in the opposite phase, thereby
weakening the propagating signal. On the other hand, in circularly-polarized systems
the reflected signal is returned in the opposite orientation, largely avoiding conflict with
the propagating signal.
Multi-path: Multi-path is caused when the primary signal and the reflected signal reach
a receiver at nearly the same time. This creates an “out of phase” problem. The
receiving radio must spend its resources to distinguish, sort out, and process the proper
signal, thus degrading performance and speed. Circularly polarized antennas respond
equally to all linearly polarized signals, regardless of the phase of polarization.
Inclement Weather: Rain and snow cause a microcosm of conditions explained above
(i.e. reflectivity, absorption, phasing, multi-path and line of sight) Circular polarization
is more resistant to signal degradation due to inclement weather conditions for all the
reason stated above.
Line-of-Sight: When a line-of-sight path is impaired by light obstructions (i.e. foliage
or small buildings), circular polarization is much more effective than linear polarization
for establishing and maintaining communication links. Once again, this is due to the CP
signal being transmitted on all planes, providing an increased likelihood that the signal
will not be adversely impacted by obstructions and other environmental conditions.
17
3.2.2 Design Process
This antenna was proposed by Wang and Chang in [51]. The CP circular patch antenna
is composed of three layers. The side and top view of the antenna are shown in Fig. 3.3
and Fig. 3.4 respectively. The first (bottom) substrate layer contains the antenna feed
line. A slot is etched on the metal layer between the feed and foam layers with a 45º
orientation relative to the feed line (Fig. 3.4). The second substrate layer is a foam layer
that let us have a distance between the two substrate layers (the feed circuit and the
radiation patch). The length of the slot helps us adjust the matching between the feed
network and the radiation patch. The third substrate layer contains a circular patch
which is perturbed by a slot and two stubs. The slot and stubs on the patch, and the 45º
aperture are utilized to optimize the axial ratio of the CP patch antenna. The objective is
to design an antenna centered at 2.45 GHz with a bandwidth that covers the 2.4GHz2.4835GHz ISM band.
Fig. 3.3 CP antenna. Side View [51]
Fig. 3.4 CP antenna. Top View [51]
Before simulating, we have to define some substrate properties. Layers should follow a
certain order like indicated in Fig. 3.3 and reproduced in ADS momentum in Fig. 3.5.
18
Also, there are some values that must be set; these correspond to the materials. Table
3.1 summarizes these parameters.
Table 3.1 Substrate parameters utilized
Arlon 25N (A25N)
Rohacell51
Permittivity (Er)
3.38
1.05
Loss Tagent (TanD)
0.0025
0.0008
Substrate Thickness (H)
0.508 mm
3 mm (width)
Conductivity (cupper)
5.813∙107
-
The design was done with the idea exposed before and was made with a trial and error
method, the dimensions of every part of the antenna where changed to optimize the final
results. In the end, we obtained the dimensions shown in Table 3.2.
Table 3.2 Dimensions of the antenna
Circular Patch (diameter)
48.9722 mm
Stubs (length / width)
3.9764 mm / 3.5 mm
Slot (length / width)
14.6345 mm / 3 mm
3 Foam layers
114 mm / 94.20 mm
Aperture (length / width )
1 mm / 40.0222 mm
Feed Line Stub (length / width )
49.8002 mm / 1.1 mm
Fig. 3.6 shows final view of the antenna‟s design made with Agilent Momentum. An
antenna prototype was built and is illustrated in Fig. 3.7. The last paragraph of this
section contains the measured and simulated performance of the antenna.
19
Fig. 3.5
Fig. 3.6 Antenna Layout
20
Fig. 3.7 Antenna
3.2.3 Antenna Measurements
The simulated impedance bandwidth of the antenna extended from 2.3 GHz to 2.72
GHz (16.73%). The result is shown in Fig. 3.8. In Fig. 3.8(a) one can see that the
antenna S-Parameters present a minimum value at 2.462 GHz. which is close to 2.45
GHz. The Smith chart plot of Fig. 3.8(b) shows a small and tight loop demonstrating the
resonance of the antenna at the desired frequency of 2.45 GHz.
The antenna S-parameters were measured using a vector network analyzer (VNA),
shown in Fig. 3.9.
(a)
21
(b)
Fig. 3.8
Fig. 3.9 Measuring the antenna‟s S11 parameter with VNA
The simulated and measured results are compared in Fig. 3.10. The measured results
(blue graphic) show that the central frequency has shifted a little bit to the left in
comparison with the simulated results (red), but there is still a good agreement between
measurements and simulations.
22
Fig. 3.10 Comparison
Fig. 3.11 (a) and (b) show the 3D radiation pattern by Agilent Momentum for the
designed antenna at 2.44GHz.
(a)
23
(b)
Fig. 3.11
To measure the antenna axial ratio we need to use a special method since we want to
measure a circularly polarized antenna.
In the anechoic chamber we have a dual linearly polarized transmitting antenna (Fig.
3.12 – Fig. 3.14). It is possible to generate a circularly polarized wave with the dual
linearly polarized antenna using a 90º hybrid in order to generate the required 90° phase
shift between the two orthogonal polarizations. Due to lack of required components we
were unable to perform this measurement. But, it is possible to evaluate the
performance of our circularly polarized antenna by employing a spinning linearly
polarized antenna as the transmit antenna in the anechoic chamber. In our case it was
only possible to rotate the test (receive) antenna (0º, 30º, 60º, etc) and therefore we were
not able to obtain spinning radiation patterns either. However, by rotating the test
antenna relative to the linearly polarized broadband transmit antenna while it is directed
at broadside we are able to estimate the Axial Ratio at broadside. In Fig. 3.12 we show
how the measurements in the anechoic chamber were done.
24
θ
Transmission
antenna
Broadside
Fig. 3.12 Anechoic Chamber measurements
Fig. 3.13 Receiving antenna
Fig. 3.14 Transmission antenna
25
Receiving
antenna
According to the ADS simulation, the Axial Ratio is less than 3dB between 2.4 GHz
and 2.5 GHz. This means that our antenna would receive either vertical or horizontal
polarization
12
Axial Ratio (dB)
10
10,03
8,618
8
7,84
7,202
6,996
6,1
5,798
6
5,148
4,414
4
4,141
3,058
3,077
1,957
1,74
2
0,787
0,478
0
2,3 2,32 2,34 2,36 2,38 2,4 2,42 2,44 2,46 2,48 2,5 2,52 2,54 2,56 2,58 2,6
Frequency (GHz)
Fig. 3.15 Axial Ratio simulations by ADS
The following plot (Fig. 3.16) shows the measured received power at broadside at 2.45
GHz, after rotating our antenna in the anechoic chamber. The observed ripple of
approximately 2dB corresponds to the axial ratio at broadside. The measured value is
larger than the one obtained in the simulation, but still is acceptable since is below 3dB.
-49,5
Power Received (dBm)
-50
0
30
60
90
120 150 180 210 240 270 300 330
-50,5
-51
-51,5
-52
-52,5
-53
-53,5
Phi Angle
Fig. 3.16 Measured Received power at broadside rotating the antenna under test relative to the transmit
antenna. The ripple corresponds to the Axial Ratio
26
Chapter 4
Rectifier
At low RF frequencies (KHz. to low MHz.), both p-n diodes and transistors are used as
rectifiers. At microwaves (1 GHz and higher), Schottky diodes (GaAs or Si) with
shorter transit times are required.
4.1
Harmonic Balance Simulation
Harmonic balance simulation is ideal for situations where transient simulation methods
are problematic. These are:

Components modeled in frequency domain, for instance (dispersive)
transmission lines.

Circuit time constants large compared to period of simulation frequency.

Circuits with lots of reactive components.
Harmonic balance methods, therefore, are the best choice for most microwave circuits
since these are most naturally handled in the frequency domain. What this kind of
simulation does is obtained frequency domain voltages and currents calculating directly
the steady-state solution.
4.2 Impedance Matching Tool
Impedance matching is the practice of designing the input impedance of an electrical
load or the output impedance of its corresponding signal source in order to maximize
the power transfer and minimize reflections from the load. Matching can be obtained
when the source impedance and the load impedance have the following relation:
27
Zs  ZL

where * indicates the complex conjugate.
ADS‟ impedance matching tool lets us design a matching network from a given circuit.
This way by simulating this circuit and by extracting its S-parameters, the software can
give us different solutions which differ, between each other, on the number of
components that are necessary to match the circuit. We selected the solution that
consists in two inductors (Fig. 4.1):
Fig. 4.1 Basic matching scheme
These two inductors represent the matching network for the circuit, and the value of
each one will be slightly different according to the type of rectifier we used. This will be
examined with more details in the next paragraphs.
4.3 Voltage Multiplier
A voltage multiplier or charge pump circuit is a circuit that takes advantage of the
diode‟s behavior to „rectify‟ a signal; depending on the signal level, the diode allows or
does not allow the current to pass. In addition to the diode a voltage multiplier circuit
uses one or more capacitors that keep the output signal at the same level while the diode
is functioning as an open circuit.
The simplest voltage multiplier consists of a parallel (or series) and a series (or parallel)
capacitor. The circuit schematic of a rectifier using a series diode is shown in Figure
28
4.12. A rectifier using a series connected capacitor followed by a parallel connected
diode is shown as Villard
Fig. 4.2 Basic Rectifier.
A voltage doubler circuit uses two diodes and two capacitors (Fig. 4.3).
Fig. 4.3 A voltage Doubler.
Additional sections of diodes and capacitors may be cascaded in order to obtain voltage
multiplier circuits of higher order (Fig. 4.4)
Fig. 4.4 A charge pump circuit (voltage multiplier)
29
4.4 Rectifier design and Optimization
In order to design a rectifier circuit we need to consider two things: (1) the rectifier
design and (2) the matching network.
The diode we decided to use is a schottky diode fabricated by Skyworks: SMS7630-079
in a package SOT-143. This package carries 2 unconnected diodes inside.
Fig. 4.5 Schottky Doide [55]
We simulated a total of six rectifiers. The first circuit that was studied was the halfwave rectifier of Fig. 4.2 using a series diode. In addition five rectifiers corresponding
to the cascaded structure of Fig. 4.4 were simulated, where each rectifier corresponds to
a different voltage multiplier order (number of diodes). The objective is to compare all
of them in terms of the output voltage and RF-to-DC conversion efficiency. The RF-toDC conversion efficiency is evaluated as
PDC

V
 DC
RL
2
PDC
 100
PRF
where RL is the load resistance at the output of the rectifier, and PRF is the available
power at the input of the rectifier.
30
The design procedure consists of a harmonic balance optimization where the rectifier
circuit capacitor(s), the output load resistor and the matching network were the
optimization variables and maximizing the efficiency , the optimization objective.
Specifically an L-matching section was used consisting of a series and a shunt inductor
as shown in Fig 4.1.
Fig. 4.6 Half-wave rectifier circuit schematic
Fig. 4.7 Full-wave rectifier circuit schematic
Fig. 4.6 and Fig. 4.7 show the circuit schematics used to design and optimize the
rectifier circuits corresponding to Fig. 4.2 and Fig. 4.3 respectively. Parasitic
components were included in the diode and capacitor models to include the effect of
their package as suggested by the part manufacturers and shown in Fig. 4.8. The circuit
block shown in red in Fig. 4.6 and Fig. 4.7 after the input voltage source contains the
matching circuit of Fig. 4.1.
31
(a)
(b)
Fig. 4.8 Diode and Capacitor‟s equivalent circuits
For each circuit under consideration the optimization was performed for an input RF
signal power of -20 dBm. The obtained efficiency and output voltage for the various
rectifiers versus the input power are shown in Fig. 4.9 and Fig. 4.10. It should be noted
that the rectifier of order one in the above Figs. corresponds to the series diode rectifier
of Fig. 4.1. The parallel diode rectifier of order one showed lower efficiency and was
not included in the plots.
It is seen that efficiency increases with input power up to a maximum value and it then
decreases for higher input power values. This is attributed mainly to the fact that as the
input power increases the input impedance of the rectifier changes and reflection losses
32
eventually become significant. The rectifier of order one has the higher efficiency for
low input power levels.
On the other hand, the rectifiers of higher order result in a higher output voltage,
although the difference is not very large for low input power values. It should be noted
however that this comparison is not fair due to the fact that each rectifier uses a different
output load resistor, as it was optimized to correspond to maximum efficiency at -20
Efficiency (%)
dBm. input power.
50
45
40
35
30
25
20
15
10
5
0
Orden 1
Orden 2
Orden 3
Orden 4
Orden 5
-20 -18 -16 -14 -12 -10 -8 -6 -4 -2
0
2
4
6
8 10
Pin (dBm)
Fig. 4.9 Comparison between different rectifier orders based on the efficiency
5
4,5
Vout (Voltios)
4
3,5
3
Orden 1
2,5
Orden 2
2
Orden 3
1,5
Orden 4
1
Orden 5
0,5
0
-20 -18 -16 -14 -12 -10 -8 -6 -4 -2
0
2
4
6
8 10
Pin (dBm)
Fig. 4.10 Comparison between different rectifier orders based on the Output voltage
We then selected two rectifiers demonstrating the highest efficiency corresponding to
order 1 (Fig. 4.2) and order 2 (Fig. 4.3) and re-optimized the circuits to include the
33
effect of the layout. This was achieved by simulating in ADS Momentum the effect of
the various microstrip pads and ground vias. In addition, the input source impedance
was changed from 50 Ohms to the simulated impedance of the designed antenna. This
was achieved by including in the harmonic balance simulation an S-parameter file
corresponding to the antenna return loss simulated from DC to 7.5 GHz in ADS
Momentum.
Tables 4.1 and 4.2 contain the optimization results for the rectifier circuit components,
for different input power levels.
Table 4.1
Rcetifier Order 1
Pin (dBm)
RL (kΩ)
L2 (nH)
L1 (nH)
-20
5,33038
7,2412
0,72624
3.34223
35,968
-10
4,22037
7.41773
0.906919
3.81323
61,77
0
0,758342
6.57248
2.29254
2.98619
66,312
10
0,1
3,89
49,9836
3.89
30,525
C_uni (pF) Nav (%)
Table 4.2
Rectifier Order 2
Pin (dBm)
RL (kΩ)
L2 (nH)
L1 (nH)
C_uni (pF)
Cs (pF)
Nav (%)
-20
9.81
1.21783
0.3965
2.9678
39.97
22,792
-10
7.4125
1.44766
0.4983
2,06348
12.9256
47,870
0
3.16
0.99
1.2127
1.85
49
65,073
10
0.25
0.1
3.26
0.76
6.83
42.6
It is seen that the required circuit component values in order to obtain a maximum
efficiency are similar for input powers -20 dBm and -10 dBm, but change significantly
as the input power increases. This essentially reflects the fact that the input impedance
of the rectifier has a strong dependence on the input power as the power increases.
Table 4.3 and Table 4.4, show the simulated optimum efficiency values for the rectifiers
for a given input power, after the component values were truncated to standard values
provided by manufacturers.
34
Table 4.3
Rectifier Order 1
Pin (dBm)
RL (kΩ)
L2 (nH)
L1 (nH)
-20
4.7
7.3
1.2
3.6
27.315
-10
4.7
7.3
1.2
3.6
58.428
C_uni (pF) Nav (%)
Table 4.4
Rectifier Order 2
Pin (dBm)
RL (kΩ)
L2 (nH)
L1 (nH)
C_uni (pF)
Cs (pF)
Nav (%)
-20
8.6
1.2
1
2.5
35
22.679
-10
7.3
1.2
1
2.5
35
47,083
After selecting the component values of Table 4.3 and 4.4 corresponding to an input
power of -20 dBm and -10 dBm (simultaneously) , the efficiency and DC output voltage
of the rectifiers produced by sweeping the input power is plotted in Fig. 4.11 and 4.12
verifying that at low input powers the rectifier of order 1 has a better performance than
the one of order 2.
Figures 4.11 and 4.12 are optimized for the lowest input power (in this case is -20dBm)
that is why the values are slightly different of those from tables 4.3 and 4.4
Efficiency (%)
70
60
50
40
30
Order 1
20
Order 2
10
0
-20 -18 -16 -14 -12 -10 -8 -6 -4 -2
0
2
4
6
8 10
Pin (dBm)
Fig. 4.11 Comparison between order1 and order 2 based on efficiency
35
2
1,8
1,6
Vout (V)
1,4
1,2
1
0,8
Order 1
0,6
Order 2
0,4
0,2
0
-20 -18 -16 -14 -12 -10 -8 -6 -4 -2
0
2
4
6
8 10
Pin (dBm)
Fig. 4.12 Comparison between order 1 and order 2 based on output voltage
4.5 Measurements
Two prototypes corresponding to the rectifiers of order 1 and order 2 were built as
shown in Fig. 4.13.
(a)
(b)
Fig 4.13 Rectifier prototypes: (a) order 1, (b) order 2.
36
The two circuits were initially populated with the components indicated in Table 4.3
and Table 4.4 corresponding to -20 dBm input power, however it was necessary to
adjust the final values in the laboratory in order to achieve a good input matching. Table
4.5 and Table 4.6 show the final values that were used in the prototypes and Fig. 4.13
and Fig. 4.14 the corresponding measured S-parameters.
Table 4.5 Final Values for the one-diode rectifier
Voltage Doubler Order 1
RL (kΩ)
L2 (nH)
L1 (nH)
C_uni pF)
5.6
4.3
1.2
3.3
Fig. 4.14 One-diode rectifier S11 parameter
Table 4.6 Final Values for the two-diode rectifier
Voltage Doubler Order 2
RL (kΩ)
L2 (nH)
L1 (nH)
C_uni (pF)
Cs (pF)
8.2
0.4
0.3
3.3
35
Fig. 4.15 Two-diode rectifier S11 parameter
37
The performance of the prototypes was evaluated by measuring the DC output voltage
of the two rectifier circuits under the following three conditions:

Increasing the input power from -20 dBm to 2 dBm at 2.44GHz.

Maintaining the input power at -20 dBm we sweep from 2.30 GHz. to 2.6 GHz.

Maintaining the input power at -10 dBm we sweep from 2.30 GHz. to 2.6 GHz
The results are shown in Fig. 4.15 – Fig. 4.20.
2500
2117
Vout (mV)
2000
1700
1500
1300
984
1000
500
78,4 116,6
149
230,2
-20
-16
-14
318
441
568
725
0
-18
-12
-10
-8
-6
-4
-2
0
2
Pin (dBm)
Vout (mV)
Fig. 4.16 One-diode rectifier Output Voltage vs. Input Power
2000
1800
1600
1400
1200
1000
800
600
400
200
0
1898
1530
1202
948,2
711
563,8
90
127
177
239,4
-20
-18
-16
-14
318,2
-12
425,7
-10
-8
-6
-4
Pin (dBm)
Fig. 4.17 Two-diode rectifier Output Voltage vs. Input Power
38
-2
0
2
120
100
86,8
93,7
101,4 100,3
94,4 93,4 97,3 96,6
88,6
84,1 85 82,8
72,5
Vout (mV)
80
62,3 58,8 59,6
60
40
20
0
2,3 2,32 2,34 2,36 2,38 2,4 2,42 2,44 2,46 2,48 2,5 2,52 2,54 2,56 2,58 2,6
Frecuencia (GHz)
Fig. 4.18 One-diode rectifier Output Voltage from 2.3 GHz. to 2.6 GHz. with -20 dBm Input Power
120
100
Vout (mV)
80
87,5
93,6
100
104,4
97,2
91,5
80
78 79,9 80,2 80,8 78,6
68,6
57,7
60
51,7 50,7
40
20
0
2,3 2,32 2,34 2,36 2,38 2,4 2,42 2,44 2,46 2,48 2,5 2,52 2,54 2,56 2,58 2,6
Frecuency (GHz)
Vout (mV)
Fig. 4.19 Two-diode rectifier Output Voltage from 2.3 GHz. to 2.6 GHz. with -20 dBm Input Power
500
423,6 430 417,2409,6427,6441,1427,6 414 415,3410,2
450
388,8
380
400 362,8
344 327
323,8
350
300
250
200
150
100
50
0
2,3 2,32 2,34 2,36 2,38 2,4 2,42 2,44 2,46 2,48 2,5 2,52 2,54 2,56 2,58 2,6
Frecuencia (GHz)
Fig. 4.20 One-diode rectifier output Voltage from 2.3 GHz. to 2.6 GHz. with -10 dBm.
39
600
Vout (mV)
500
501,6 495
476,6
474
443,3
436 434 450 457 458 451 419
423
372
400
343 335
300
200
100
0
2,3 2,32 2,34 2,36 2,38 2,4 2,42 2,44 2,46 2,48 2,5 2,52 2,54 2,56 2,58 2,6
Frecuencia (GHz)
Fig. 4.21 Two-diode rectifier output Voltage from 2.3 GHz. to 2.6 GHz. with -10 dBm.
Finally, the rectifier efficiency was measured, using the input power, output voltage and
load resistor values. The results are indicated in Table 4.7.
Table 4.7 Efficiency at 2.45 GHz.
Rectifier
Order 1
Order 2
PRF (dBm)
Vout (mV)
η (%)
-20
78.4
12.19
-10
441
38.58
0
1700
46.44
-20
90
10.09
-10
425.7
24.47
0
1530
31.71
The measured results confirm the fact that the rectifier circuit using a single diode
shows the best performance, however the measured efficiency values are less than the
simulated ones of Table 4.3 and Table 4.4. The reason is attributed to additional losses
due to the prototype manufacturing, component yield variations and an inaccurate
estimation of the diode and lumped component parasitics which resulted in the need to
adjust the rectifier matching circuits in the laboratory.
40
Chapter 5
Regulator
The objective of this chapter is to design a test-board for the Texas Instruments
regulator circuit, to be subsequently used following the rectifier. Based on the
component datasheet and following the manufacturer recommendations a circuit board
was designed using the layout features of ADS Momentum. A prototype was built and
its performance was verified in the laboratory.
5.1.1 Integrated Circuit TPS6120x
A TPS6120x is an alternative solution for products that are powered by a single-cell,
two-cell, or three-cell alkaline, NiCd or NiMH, or one-cell Li-Ion or Li-polymer battery.
When there is a low current flowing through the chip, it enters the Power Save mode,
which can also be disable. The maximum average input current is limited to a value of
1500 mA and the output voltage can be chosen from 1.8 V to 5 V. The device is
packaged in a 10-pin QFN PowerPAD™ package (DRC) measuring 3 mm x 3 mm.
Table 5.1 Recommended operating conditions [53]
MIN
NOM
MAX
UNIT
VSS
Supply Voltage at Vin
0.3
5.5
V
TA
Operating free air temperature range
-40
85
ºC
TJ
Operating virtual junction temperature range
-40
125
ºC
41
5.1.2 Design Process
As for all switching power supplies, the layout is an important step in the design,
especially at high peak currents and high switching frequencies. If the layout is not
carefully done, the regulator could show stability problems as well as EMI problems.
Therefore, we will use wide and short traces for the main current path and for the power
ground tracks. The input and output capacitor, as well as the inductor should be placed
as close as possible to the IC. The schematic recommended by Texas Instruments is the
following (Fig. 5.1).
Fig. 5.1 Regulator Schematic [53]
42
All the components that appear in the previous schematic have specific values to make
the chip work.
Table 5.2 Regulator Components
Component
Value
Size
C1
10 uF
0603
C2, C3
0.1 uF
0603
C4
Open
-
C5, C6
10 uF
0603
L1
2.2 uH
0.118 x 0.118
R1
91 Ω
0603
R2
0Ω
-
R3
Open
-
R4
1 MΩ
0603
R5
178 kΩ
0603
Now that we have the size of all the components we can design the board layout. It‟s
important to remember that since the regulator works in DC we don‟t have to worry
about the effect of the strips and pads in the layout.
Fig. 5.2 Regulator Circuit Layout Top view
43
Fig. 5.3 Regulator Circuit Layout Bottom View
After designing the regulator layout (Fig. 5.2 and 5.3) we are ready to solder all the
components we listed in table 5.2The final prototype is shown in Fig. 5.4 and 5.5
Fig.. 5.4 Regulator Circuit Top View
44
Fig. 5.5 Regulator Circuit Bottom View
After testing the circuit we confirmed the operation of the regulator as described in the
datasheet. Based on the chosen component values a 3.3 Volt regulated output voltage
was expected. The regulator chip starts producing the desired output voltage when the
input voltage rises to 400 mV. Due to hysteresis phenomena, the regulator operated
until the input voltage decreased to 250 mV.
45
Chapter 6
Conclusions and Future Work
There are some important conclusions we can point out:
The rectifier with the consisting of a series connected diode demonstrated the highest
efficiency for low input power densities of -20 dBm to -10 dBm. Moreover, the
efficiency of all rectifier circuits increases for higher input power values. Finally, the
use of circularly polarized antennas helps capture ambient electromagnetic waves with
arbitrary polarization. Our system has proved to be an RF recycler that could be very
useful in indoor applications like wireless sensors.
Future work that can be done following this project is to design a UWB rectenna or
multi-band rectenna. Another potential topic of future work could be the use of flexible
substrates for the antenna like PET, paper and textile, these materials give us the chance
to make our antenna low profile, and conformal. Finally, we still have to make some
indoor measurements to test the work range of our system.
The following paper using the results obtained in this thesis was submitted to the PIERS
conference 2011 in Morocco.
[1]
O. A. Campana Escala, G.A. Sotelo Bazan, A. Georgiadis, and A. Collado, 'A
2.45 GHz Rectenna with Optimized RF-to-DC Conversion Efficiency,' submitted
to Progress in Electromagnetics Research Symposium (PIERS), 20-23 March
2011, Marrakesh.
46
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