<,~ Substrae A New Transformation of Bandpass Filter to Bandstop Filter Using Multilayer-Technique and U-Defected Ground Structure DGS Ahmed BoLJTEJDAR, Anatoliy BATMANOV', Jan MACHAci, Edmund BuRTE', Abass OMAR], IEEE, Fellow 'Chair of Microwave and Communication Engineering University of Magdeburg, Germany 2Faculty of Electrical Engineering, Czech Technical University, Prague, Czech Republic Ahmed.Boutejdargovgu.de Abstract. A novel compact microstrip bandpass/Bandstop filters realized by combining new Multilayer Method with electrically coupled microstrip U-shaped DGS resonators, is proposed The proposed filters have low insertion loss and are compact in size due to the slow-wave effect. They also have sharp transition regions due to the presence of twotransmission zeros on both sides of their passband. The measured center frequency, bandwidth and insertion loss are 3.4 GHz, 4O0'o, and 0.5 dB respectively. The simulated and measured results show good agreement and validate the proposed approach. filters, especially narrow-band bandpass filters which play an important role modem communication and electronic systems [1]-[2]. In order to obtain compact three-pole microstrip bandpass filters with two transmission zeros, low rejection band performance, low insertion loss in passband and high selectivity, several structures were proposed such as the filters using end-coupled slow-wave resonators, slow-wave openloop resonator filters and slow-wave open stub-tapped resonator filters. Another techniques involve employing cross coupling and Quasi-elliptic function filters which are able to place the transmission zeros near the cutoff frequencies so that higher selectivity with less resonators can be obtained. Keywords U-Resonator 50Q.-Microstrip line DGS, Microstrip slots, Suspended layer, BPF, BSF. Substrate IUha G 1. Introduction Metallic Ground plane Recently, defected ground structures (DGS) and electromagnetic band gap (EBG) structures have received increased attention because of their use in mobile communication systems which require compact high performance filters and couplers. One of the very successful approaches to achieve siginifcant size reduction is to use DGS components which also has the capability of suppressing harmonics. DGS elements can be used in various kinds of components such as lowpass filters and bandpass filters as well as RF phase shifters. DGS, which evolved from EBG are realized by etching certain patter in the metallic ground plane of a microstrip line which perturbs the curent distribution causing an increases in the effective inductance and capacitance of the line. Thus, a DGS elements is equivalent to an LC circuit. Planar bandpass filters [1] have been extensively studied and exploited as key circuit blocks wit oprtn fucin of inbn trnmiso an out-of-1 ban reecio. To mee th reureet in moe .irls communication, much effort has been made in the past years. to develop a variety of compact bandpass filter with sharp and dee reeto ousd the pasbn by genrain tranmisionzersorattnuaionpols. Rcen adanc in high-empeaturesupecondcting (HTS circits nd , . has . , ., microwave monolithic integratedl circuits ..(MMIC) additionally stimulated the development Of various planar 978-1-4244-2138-1/08/$25.OO ©)2008 IEEE Fig. 1. Three-dimensional view of the U-Head-DGS cell. In order to improve the selectivity and efficiency of spectrum .. utilisatn, erswit two or mrestorasmission zerosthav bed aed . Usn wo 4resnto with a stub[3 trappe inveerr lolwa proposedstopachiein ahsingle tansmssonzero at origh toto zero mpedance i ch t attached open-ended stub iS at attributed i X/2l. ine Another ttwo ttransmission zeros resonator). s . A in [4], were realized using open stub lines and DGS-circles. In [3], a slow-wave resonator filter using two coupled hairpin microstrip folded Lines was presented. The bandpass filter, designed at fundamental resonant frequency of the resonator, show low insertion loss in the passband. In this paper, a new type of compact microstrip bandpass ' -G fitr,wt'lwwv fetraie sn resonators and Multilayer Method has been developed. Transmission zeros can be implemented on both sides of the passband. The proposed filter iS fabricated and measured. The results were in good agreement of the ~~measurement siuaonrul. thseparated 2. Characteristics of the DGS 3. Design of the proposed Compact BPF The proposed U-DGS in Fig. 1-2 is etched in the ground plane and consists of two capacitive arms, which are connected to a rectangular slot, with the same dimension as shown in Fig. 2. The etched slot (DGS) is equivalent to a capacitance. The metal area between the two arms on the top layer corresponds to an inductance. The conventional circuit parameters can be extracted from an electromagnetic simulation by matching to a one pole Butterworth band stop filter response, as in [5]. The U-Slot in the ground plane excited by the 50Q line acts as a parallel resonant circuit [5]. It can be modeled by a parallel LC circuit as shown in Fig. 2. The values of L and C can be computed using: In order to improve the performance of the previous bandpass filter shown in Fig. 3, a multilayer structure is used. The new structure is similar to the original filter but the central DGS resonator is moved to the bottom layer as shown in Fig. 3. This was found to improve the performance and reduce the overall size of the filter. The new bandpass filter has the same bandwith (400 o) and the same center frequency (fO:3.4GHz) but with improved passband characteristics. In order to obtain the coupling matrix of the new topology, the specifications of the filter are defined and then the desired parameters are extracted by using an optimization-based scheme [6-7]. The coupling coefficient and quality factor curves are then used 25 2 pF & C= ( )J f Cp C nH (1) The values of the cut-off frequency f, and resonance frequency fp can be found from the transmission characteristics of the U-slot. The simulation results of the Uslot show one-pole low-pass filter characteristics. It is clear that employing the slot in the metallic ground plane increases the effective permittivity, leading to an increase of the effective inductance of the microstrip line. From the Figs. 2. we can see the dependence of the resonance frequency (cutoff frequency) on the dimensions of the U-shape on the top and bottom layers. The etched arm has a significant effect on the resonance frequency. Actually, it is well known that an attenuation pole can be generated by a combination of inductive and capacitive elements. This explains the frequency characteristic of the proposed U-DGS-element. Fig. 2 shows that if b is kept constant while varying d, it is easy to control the positions of the (cutoff) and attenuation poles. This means that the length of gap (arm) controls the effective series inductance of a microstrip. The microstrip 12 to realize the obtained coupling coefficients. In our case the third order filter is required to designed to have a bandwidth BW = 1300 MHz, return loss RL = 20 dB, and center frequencyfo = 3.4 GHz. The obtained coupling matrix from the optimization scheme is 0 M L0.721 0.721 (2) 0 and the external quality factors are qin= qout= 1.24. To realize the normalized coupling matrix and quality factors, we use the required fractional bandwidth FBW = BW/fo. The actual (denormalized) coupling matrix becomes and Ql = Q2 = 3.1 where m = FBW x M , and Q = q/ FBW. The m-coupling coefficients will be inserted in the The unknown distance s is 2mm. The proposed DGS-Bandpass filter was 0mF 0.288 o.288 o (3) 50Q-Microstrip line U-Resonator 10 < \3-jX ~~~~~c 10 trate 0 b > ~~ 4 '' - - < 2o U- DGS 0 0 11 22 33 44 Lenght (d) of the arm in mm 55 66 Fig.2. ComparisonofresonancefrequencyofDGS(-) and Mircostrip resonator ). line on the top of the substrate in Fig. 2 has a width of w=1 .9mm to obtain a 50Q2 characteristic impedance of the microstrip line. The substrate dielectric constant is 3.38 and its height is h=0.8 13mm. The dimensions shown in Fig. 3 are g =lmm, b =3mm and d =1 1mm. The DGS cell is simulated using Microwave Office. Simulation results are depicted in Fig. 2, which shows the characteristics of a one-pole LPF. X i~~~ F Metallic Ground ~~~~ ~~~~~plane Fig. 3. Three-dimensional view of the new U-Bandpass filter. simulated on a Rogers R04003 substrate experimental curve [6] in order to get the optimal distance between the DGS relative dielectric constant £r of 3.38 and a ~~~~~~~~~~resonators.with thickness h of 0.813mm. Simulation is performed using Microwave Office and CST Microwave Studio.M. All the dimensions ofthe U-slot are g=lmm, b=3mm and d=ll mm. The simulation results ofthe bandpass filter are shown in Fig. 5. Although the filter consists of three resonators, only two poles exist in the passband. This is because one of the resonators is in the bottom layer. 4 Design and Fabrication of the BPF The simulation results showed that the designed filter has a good sharpness factor, symmetrical response and smaller losses in the pass band as shown in Fig. 5. In order to verify the simulation results, the filter was fabricated and measured using an HP8722D network analyzer. The measurement results are shown in Fig. 5. together with the simulation results. A very good agreement between the simulated and measured results is observed. In the passband, the measured insertion and return loss were less than 0.7dB and 20dB, respectively. The results shows significantly improved performance over the filters previously presented in [5-6]. The BPF was simulated and fabricated on a substrate with a relative dielectric constant £r of 3.38 and a thickness h of 0.813mm. Simulation is performed using CST Microwave Studio and Mocrowave Office. Fig. 4 shows photographs of the fabricated BPF filter. The total area is 20 x 15Mmm2. 50Q-Microstrip line Ue a U-Resonator _ Metallic Ground plane Fig. 6. Three-dimensional view of the cascaded U-bandstop filter. performance because the losses is not negligible in pass band and the stop band is not large enough. In order to improve these characteristics and in the same time to reduce the size of the filter, we have used another reduction method, which will be shown in later chapter. -10 ~~~~~~-15 -2 -06 -35 pg1 3 ! 1X1 * l | 5i1 E _ -40 i Si11 s21 Fig. 4. Photograph of the fabricated U-DGS BPF. P -10 0 6 8 10 -L m-30 uo -3011 -40 -50 4 Frequency[GHz] Fig. 7. Simulated S-parameters ofthe proposed cascaded BSF. --- -20 2 6. Design of the Multi-Layer BSF In order to improve the performance of the Previously structure and further reduce its size, we moved one of the - Measurement ~EM-Simulation -601 2 3 4 5 6 7 8 9 Frequency[GHz] Fig. 5. Measured and Simulated S-parameters of the proposed BPF. - 5. Design of the Cascaded BSF microstrip resonators to the upper layer, thus the new compact PSF will be consist of two connected microstrip U-resonators on the Top layer and one DGS-U-slot on the ground plane. This proposed geometrical idea is based on the use of several layers on top of each other. The new structure is similar to three cascaded structure but the central resonator is moved to theBottom layer. The simulation results of the resultingcom- The Fig. 6. shows that the transformation of band-pass filter band stop filter is feasible by connecting the three Microstrip U-elements together. The 3 U-resonators are similar and it presents a 3 pole cascaded band stop filter. The Fig. 6. shows the cascaded structure, which is designed on a R04003S.srt substrate with a relative dielectric constant £r of 3.38 and a thickness h of 0.8 13mm. in this case, the ground plane is full- / copper with a Thick of 35p~m and it is separated from top /_ layer through the substrate. Fig. 7. shows the simulated parameters ofthe cascaded band stop filter. The filters'answer shows that the structure has an insertion loss of 2 dB from DC to 4.3GHz and the return loss is - 6dB over the both passbands The esig of te casadedstrucure desn' givegood 50Q-Microstrip line /Rot U-Resonator 111\ ; ~_ U- DGS __ _ 7 \ Metallic GIround plane Fig. 8. Three-dimensional view of the proposed U-DGS-bandstop filter. the etched arm is equivalent to a series inductance. So, the DGS unit is equivalent to a resonant circuit, which is shown in Fig. 2. the etched arm length. The slot head dimensions were kept constant and the length of the arms was varied. The simulation results are shown in Fig. 10. and Fig. 11. the attenuation pole location moves up to a higher frequency, while the length decreases. -pact structure are much better, compared to the conventional BSF structure. As shown in Fig. 9. and Fig. 8. We designed and simulated this filter using AWR. This new modification of the structure does not have a significant influence on the performance of the filter as compared to the previous ones. We can use the top and Bottom layers without sacrificing the good response of the filter. The cutoff and resonance frequencies did not change from their previous positions, but the advantage is that, the new BSF is 35% more compact than the conventional [3], as Fig. 8 shows. 10 0~~~~~~~~~~~~~~~~~~~~~~~1 / C~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~~" -10X d=1om; Ci) -30 &m -06 -40 811~~~~~~~~~~~~~~~~-5 -50 j~ ~ ~ t -60 2 4 6 2 8 Frequency[GHz] ~=m Frequency[GHz] l0 Fig. 11. Simulated 21-parameters for different length, d. Fig. 9. Simulated results of the new compact BSF. 8. Conclusion 7. Tuning of The Filter Characteristics A new U-bandpass filter with multiple transmission zeros for sharp transition band has been presented in this paper. In order to realise a compact, symmetrical structure and to simplify the implementation, DGS-method and coupling method were used. The measured insertion loss and return loss are less than 0.7dB and 20dB in the passband of 1.3GHz at center frequency 3.2GHz, respectively. The proposed Filter was designed, simulated, fabricated and measured. Good agreement between simulated and measured results has been achieved. In order to investigate the frequency characteristics of the etched slot, we simulated the DGS unit section using Microwave Office. The variation of the dimensions of the etched gap shifts the cutoff frequency and the attenuation pole location in the frequency domain. As is well known, a resonance frequency can be generated by a combination of inductive and capacitive elements [3]. The etched gap area, which is placed under the microstrip line, corresponds to capacitance and the metal area, which is between the both arms is equivalent to a series inductance. So, the DGS unit is equivalent to a resonant circuit, which is shown in Fig. 2. The parameters of this DGS equivalent circuit have been found using curve-fitting. The found results were: C =0.33pF and L 2.33nH. Next we investigated the effect of 0.33pF of References [1] Awida, Mohamed; Boutejdar, Ahmed; Safwat, Amr; El- Hennawy, Hadia; Omar, Abbas Multi-bandpass filters using multi-armed open loop resonators with direct feed In: 2007 IEEE MTT-S International Microwave Symposium , Honolulu, Hawaii, June 03 - 08, 2007. <zrX7 [Piscataway, NY]: IEEE Operations Center, S. 913-916 [2] A. Abdel -Rahman, A. K. Verma, A. Boutejdar and A. S. Omar, ,,Compact stub type microstrip bandpass filter using defected ground -plane," IEEE Microwave and Wireless Components Letters, vol. 14, ---pp. 136-138, 2004. (MTT- Journal). 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