Proposal of Three-phase Two-level Unidirectional SEPIC PWM Rectifiers with High Power Factor Flabio Alberto Bardemaker Batista Carlos Henrique Illa Font Dept. of Electronics, Campus Florianópolis Federal Institute of Santa Catarina (IFSC) Florianópolis, Brazil flabio@ifsc.edu.br Dept. of Electronics, Campus Ponta Grossa Federal University of Technology – Paraná (UTFPR) Ponta Grossa, Brazil illafont@utfpr.edu.br Abstract—This paper presents the initial theoretical analysis of three-phase two-level unidirectional SEPIC PWM rectifiers. The rectifiers operate in CCM (continuous conduction mode) with high power factor and output voltage control. Converter switching stages are analyzed for single-phase structure and the three-phase Y-connected and the Δ-connected rectifiers are derived from it. These rectifiers have the advantages of providing high power factor with low input filtering effort, as Boost rectifiers, and lower output voltage level, as Buck rectifiers. The disadvantage is the increase of component count, due the need for additional capacitors and inductor per phase. The control strategy is presented with a description of the objectives of the mains current control loop and the output voltage control loop. Simulation results from a rectifier with 380V input voltage, 400V output voltage, 20kHz switching frequency and 6kW output power are also presented. I. INTRODUCTION PFC Boost AC-DC converter topologies are widely used as front-end stages both in single-phase and three-phase applications. The main advantages of Boost PFC rectifiers are low input filtering effort, high efficiency, sinusoidal mains current and controllability of output voltage [1-3]. Therefore, for three-phase 380V or 440V AC mains voltage, Boost PFC rectifiers produce an output voltage too high to directly feed many types of loads in applications as Electric Vehicle (EV) battery charging [4], UPS systems and telecom power supplies [5]. In the applications named before, a DC-DC step-down stage is required after the PFC Boost rectifier. Thus, this increases component count and decreases the efficiency. Moreover, the blocking voltage stress on the power semiconductors of the DC-DC converter stage is defined by the Boost converter output voltage and not by the lower load voltage level. Buck-type AC-DC rectifiers are solutions for front-end stage with lower output voltage level. Therefore, even in CCM (continuous conduction mode), the input current of Buck Identify applicable sponsor/s here. (sponsors) converter is discontinuous. Then, for high power factor operation, a large and bulk LC filter is needed at the input [67]. This paper proposes the use of three-phase SEPIC rectifiers for feed loads that require low DC voltage level in systems that require high power factor. This solution has the advantages of providing high power factor with low input filtering effort, as Boost rectifiers, and lower output voltage level, as Buck rectifiers. The disadvantage is the increase of component count, due the need for additional capacitors and inductor per phase. In the literature, some topologies of three-phase SEPIC rectifiers were presented in [8-14]. The topology presented in [8] is a three-level unidirectional SEPIC-type rectifier, operating in continuous conduction mode and suitable for medium power applications. This topology employs only three active switches, unlike the topology presented in [11], whose employs six active switches in the two level version. The system proposed in [9] is composed by a three-phase diode-bridge rectifier cascaded by a SEPIC DC-DC converter operating in CCM. The structure is simple and robust. The input currents do not follow a sinusoidal shape leading the system to operate with high total harmonic distortion. The topologies presented in [10], [12-14] use three singlephase modules and provide galvanic isolation between AC mains and DC load. The proposed rectifiers presented in [10], [12-13] operate in CCM and they are intended for use in low power applications. The topology presented in [14] operates in discontinuous conduction mode (DCM). This proposal has the advantage of providing unity power factor, without the use of any current sensor and currents control loop because in DCM the system has a resistive-load behavior. First, the Y-connected rectifier topology is presented in Section II. Section III of this paper presents the theoretical analysis of a single-phase leg and the behavior of the threephase system. Section IV shows the control scheme. Simulation results are presented in Section V. Finally, the discussions for the Δ-connected rectifier topology are presented in Section VI. II. THE PROPOSED Y-CONNECTED THREE-PHASE SEPIC PWM RECTIFIER The proposed Y-connected three-phase SEPIC rectifier is presented in Fig. 1. This unidirectional topology is the twolevel version of the three-level one presented in [8]. It has three switches and each single-phase leg is connected in a Y configuration. The proposed Y-connected three-phase SEPIC rectifier is capable of providing high power factor with low filtering effort. The output voltage can be controlled to be lower, equal or higher than the mains input voltage. III. THEORETICAL ANALYSIS A. Single-phase Analysis The operating modes for a single-phase leg are presented in Fig. 2, considering that all semiconductors are ideal and the system operating in steady state. In continuous conduction mode (CCM), there are four operating modes, where two are for input current greater than zero and two for the input current lower than zero. In the first operating mode, S1 is turned on and the input voltage v1 is greater than zero. The energy from input source v1 is transferred to the inductor L1. Capacitors C1 and C2 transfer its energy for inductor L2 through S1. The output capacitor Co supplies the load. This operating mode ends when S1 is turned off. Figure 2. Operating modes for a single-phase leg: a) first, b) second, c) third and d) fourth. The analysis for the first operating mode yields to (1), (2), (3) and (4): In the second operating mode, S1 is off and the input voltage v1 is greater than zero. Input source v1, inductors L1 and L2 transfer the energy to the output, charging output capacitor Co and supplying the load, and charging capacitors C1 and C2. This operating mode ends when S1 is turned on again. v L1 ( t ) = v1 ( t ) (1) v L2 ( t ) = v C1 ( t ) + v C2 ( t ) (2) iCo ( t ) = − Third and fourth operating modes are similar to first and second operating modes, respectively. But in these last two operating modes the input voltage v1 is lower than zero. Vo Ro iC1 ( t ) = iC2 ( t ) = −iL2 ( t ) where: - v1(t): mains voltage; - vL1(t): voltage across inductor L1; - vL2(t): voltage across inductor L2; - vC1(t): voltage across capacitor C1; - vC2(t): voltage across capacitor C2; - Vo: output voltage; - Ro: load resistance; - iCo(t): current in capacitor Co; - iC1(t): current in capacitor C1; Figure 1. The proposed Y-connected three-phase SEPIC PWM rectifier. - iC2(t): current in capacitor C2; (3) (4) ( For the second operating mode, the analysis conducts to (5), (6), (7) and (8): v L1 ( t ) = v1 ( t ) − v C1 ( t ) − v C2 ( t ) − Vo = − v1 ( t ) + Vo (5) v L2 ( t ) = −Vo (6) ( ) v D5 ( t ) + v D6 ( t ) = − v C1 ( t ) + v C2 ( t ) + Vo = - iL2(t): current in inductor L2. ) VD5max = VD6 max = V1pk + Vo 2 (13) (14) where: - vD5(t): voltage across rectifier diode D5; - vD6(t): voltage across rectifier diode D6; V iCo ( t ) = iL1 ( t ) + iL2 ( t ) − o Ro (7) iC1 ( t ) = iC2 ( t ) = iL1 ( t ) (8) - VD6max: maximum voltage across rectifier diode D6; Considering the volt-second balance in inductors L1 and L2, from (1), (2), (5) and (6), results in (9) and (10). v L1 ( t ) Ts ( ) = 0 ⇒ d ( t ) . v C1 ( t ) + v C2 ( t ) + Vo = = −v1 ( t ) + v C1 ( t ) + v C2 ( t ) + Vo v L2 ( t ) Ts ( - VD5max: maximum voltage across rectifier diode D5; - V1pk: mains peak voltage. During second operating mode, S1 is turned off. The voltage across switch S1 is given by (16), through (15). (9) ) = 0 ⇒ d ( t ) . v C1 ( t ) + v C2 ( t ) + Vo = Vo (10) v S1 ( t ) = v C1 ( t ) + v C2 ( t ) + Vo = v1 ( t ) + Vo (15) VS1max = V1pk + Vo (16) where: - vS1(t): voltage across switch S1; - VS1max: maximum voltage across switch S1. where: B. Three-phase Analysis For three-phase analysis, it is considered the rectifier’s behavior in 60 degrees of the mains period. Assuming the analysis in the sector where 60o ≤ ω.t ≤ 120o, the mains currents have the behavior presented in (17). - d(t): duty cycle; - Ts: switching period; - < >Ts: average value in the switching period. Substituting (10) in (9), it yields to (11). v C1 ( t ) + v C2 ( t ) = v1 ( t ) (11) Assuming that capacitors C1 and C2 have the same capacitance, it yields to (12). ⎧i1 ( t ) ≥ 0 ⎪⎪ ⎨i2 ( t ) ≤ 0 ⎪ ⎪⎩i3 ( t ) ≤ 0 (17) (12) Considering that, in the three-phase system, each phase will have the same operating modes as single-phase leg, the operating modes for three-phase rectifier is presented in Fig. 3. Therefore, the capacitors C1 and C2 are charged with a half of input voltage level. The voltage across capacitors C1 and C2 are important parameters for describing the maximum voltage across semiconductors. Since the three-phase rectifier has three active switches and each switch can assume two states, it results in eight different operating modes for the selected sector. As notation, 0 means that the switch is off and 1 means that the switch is on. During the first operation mode, the switch S1 is turned on and the rectifiers diodes D5 and D6 are blocked. The voltage across rectifier diodes is given by (14), through (13). Therefore, in the operating mode 000 the three active switches are off while in the operating mode 111 all switches are on. v C1 ( t ) = v C2 ( t ) = v1 ( t ) 2 First operating mode (000) Second operating mode (001) Third operating mode (010) Fourth operating mode (011) Fifth operating mode (100) Sixth operating mode (101) Seventh operating mode (110) Eighth operating mode (111) Figure 3. Operating modes for the sector where 60o ≤ ω.t ≤ 120o. Fig. 4 shows the equivalent circuit for operating modes 1 (000) and 5 (100). In these operating modes, the capacitors among different phases are placed in parallel. So, it means that the capacitors cannot be charged with the mains input voltage level. Since the capacitors among different phases are placed in parallel, it imposes a restriction for defining appropriate vectors in a space vector modulation. Even if the operating modes where the capacitors are placed in parallel are avoided, the available vectors from the others operating modes are dependent on the input voltage. Thus, the synthesized vector cannot be obtained adequately, as in the space vector modulation strategy proposed for Boost rectifiers [2-3]. This behavior is different from the single-phase case and a proper modulation strategy should be searched for three-phase rectifier. C. Start-up Operation The SEPIC rectifier presents an advantage during the startup when compared with Boost rectifiers. At the initial start-up all capacitors, including the large output capacitor Co, are discharged. When the three-phase rectifier is turned on, an inrush current surge charges all capacitors. The inrush current produces little consequence because the capacitances C1, C2, C3, C4, C5 and C6 are small and charge rapidly. Then, the output bulk capacitor is charged slowly to the output voltage level, under an inherent current limit control. This behavior is completely different of a Boost rectifier, whose inrush surge has great magnitude because it charges the output capacitor directly. Boost rectifiers need an inrush current circuit with additional inrush resistors and an AC contactor. IV. CONTROL STRATEGY The control scheme of the SEPIC rectifier is showed in Fig. 5. It is composed by three current control loops and a voltage control loop. The voltage control loop provides DC output voltage regulation and the references for the current control loops. The current control loops impose sinusoidal shapes for the input currents without displacement factor. The gains and the variables presented in Fig. 5 are described as follow: • kIi: current sensors gains; • kVi: mains voltage gains; Figure 4. Equivalents circuits for a) first operanting mode (000) and b) fifth operating mode (100). The control strategy is based on the multiplier approach for imposing the current references. This concept is the same traditional scheme used for three-phase Boost rectifiers. The modeling and control design will be omitted here for the sake of brevity. A sinusoidal PWM modulation is used for generating the command signals. A sawtooth carrier signal is used for the three signal comparators. V. SIMULATION RESULTS A numeric simulation was performed with the specifications presented in Table I, using software PSIM 9.0.4. • kVo: output voltage gain; • km: multiplier gains; • VoRef: system reference voltage; • I1Ref, I2Ref and I3Ref: current reference voltages; • Hi1(s), Hi2(s) and Hi3(s): current controllers; • Hv(s): output voltage controller; • PWM1, PWM2 and PWM3: PWM modulators. TABLE I. SIMULATION PARAMETERS Parameters Input mains line voltage Output voltage Mains frequency Switching frequency Output power Inductors L1, L2 and L3 Inductors L4, L5 and L6 Capacitors C1, C2, C3, C4, C5 and C6 Capacitor Co Values 380 V 400 V 60 Hz 20 kHz 6000 W 4 mH 900 µH 330 nF 1500 µF Figure 5. Control scheme of three-phase SEPIC rectifier. The three-phase input currents waveforms are shown in Fig. 6. The currents present sinusoidal shape, allowing high power factor. Figure 7 presents the waveforms of input voltage and input current for phase 1 and the output voltage. The output voltage level is 400V for 220V input phase voltage (380V input line voltage). In that case, SEPIC rectifier is operating as stepdown converter. Figure 8 presents the waveforms of input currents and output voltage during the start-up. One can observe that there are no several spikes in the input currents and the output capacitor is charged slowly, without any auxiliary circuitry for start-up. Figure 6. Input currents waveforms. Figure 9 shows the voltage across capacitor C1 and C2. It is observed that, for the sinusoidal PWM modulation adopted, the capacitor voltage is asymmetrical and with 900V peak voltage. Figure 7. Output voltage, input voltage v1 and input current i1 (multiplied by 10) waveforms. Figure 11. Input currents waveforms for the Δ-connected three-phase SEPIC PWM rectifier. Figure 8. Output voltage and input currents waveforms during start-up. VII. CONCLUSIONS Three-phase unidirectional Y-connected SEPIC rectifier and Δ-connected SEPIC rectifier are presented as power factor correctors. The switching stages are analyzed for the singlephase leg and the behavior for the three-phase system is presented. The simulation results show that the proposed unidirectional rectifiers are operating with high power factor and that the output voltage is in the desired value. Also, the start-up behavior of SEPIC rectifier is verified by simulation. Figure 9. Capacitors C1 and C2 voltage waveforms. VI. DISCUSSION FOR THE Δ-CONNECTED THREE-PHASE SEPIC PWM RECTIFIER Fig. 10 shows the Δ-connected three-phase SEPIC PWM rectifier topology, where each single-phase leg is connected in a Δ configuration. Possible advantages of this topology are lower input current total harmonic distortions and increase of efficiency, as observed in [3] for Boost rectifiers. In the case of a Boost rectifier, with a proper modulation strategy, for the active switches, conduction losses and switching losses are smaller in Δ-connected topology. The three-phase input currents waveforms for the Δconnected three-phase SEPIC PWM rectifier topology are shown in Fig. 11. The theoretical analysis shows that the three-phase SEPIC rectifier cannot operate as three single-phase converters, since the capacitors will not be charged with the input voltage level. 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