346 IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 52, NO. 1, JANUARY 2004 [3] P. H. Harms, J.-F. Lee, and R. Mittra, “A study of the nonorthogonal FDTD method versus the conventional FDTD technique for computing resonant frequencies of cylindrical cavities,” IEEE Trans. Microwave Theory Tech., vol. 40, pp. 741–746, Apr. 1992. [4] E. A. Navarro, C. Wu, P. Y. Chung, and J. Litva, “Application of PML superabsorbing boundary condition to nonorthogonal FDTD method,” Electron. Lett., vol. 30, no. 20, pp. 1654–1656, 1994. [5] , “Some considerations about the FDTD method in general curvilinear coordinates,” IEEE Microwave Guided Wave Lett., vol. 7, pp. 396–398, Dec. 1994. , “Sensitivity analysis of the nonorthogonal FDTD method applied [6] to the study of square coaxial waveguide structures,” Microwave Opt. Technol. Lett., vol. 8, pp. 138–140, Feb. 1995. [7] S. D. Gedney and J. A. Roden, “Numerical stability of nonorthogonal FDTD methods,” IEEE Trans. Antennas Propagat., vol. 48, pp. 231–239, Feb. 2000. [8] J. A. Stratton, Electromagnetic Theory. New York: McGraw-Hill, 1941. [9] J. G. Maloney and G. S. Smith, “The efficient modeling of thin material sheets in the finite-difference time-domain (FDTD) method,” IEEE Trans. Antennas Propagat., vol. 40, pp. 323–329, Mar. 1992. [10] P. D. Einziger and L. B. Felsen, “Rigorous asymptotic analysis of transmission through a curved dielectric slab,” IEEE Trans. Antennas Propagat., vol. AP-31, pp. 863–870, Nov. 1983. [11] A. Sadigh and E. Arvas, “Deformation of the horizontal radiation pattern of TV transmitting antennas due to a thin dielectric radome,” IEEE Trans. Antennas Propagat., vol. 40, pp. 942–949, Aug. 1992. Design of a Small and Low-Profile 2 2 Hemispherical Helical Antenna Array for Mobile Satellite Communications H. T. Hui, Edward K. N. Yung, C. L. Law, Y. S. Koh, and W. L. Koh 2 Abstract—A small and low-profile 2 2 hemispherical helical antenna array was designed for INMARSAT satellite reception. With only four elements fed by a simple network, the array can produce a gain of 15 dB, a 3-dB axial ratio bandwidth of nearly 14%, a cross-polarization level of smaller than 20 dB over the half-power beamwidth, and a radiation pattern with a sidelobe level of 20 dB. These characteristics are better than those obtained by previously proposed INMARSAT-M antennas. 0 0 Index Terms—Antenna array, circular polarization, hemispherical helical antenna, satellite communications. I. INTRODUCTION Mobile satellite communications rely very much on the design of good vehicle antennas [1]. In order to combat the problem of polarization change of the electric field by the atmosphere, circular polarized antennas are generally used. In the INMARSAT-M system, the mobile vehicle antenna is required to be small in size and have a relative high gain of 13–16 dB. Several circular polarized antennas or antenna arrays have been suggested for use in this system [2], [3]. However, they are either too large in size and require additional design for feeding network [2] or their gain is too low [3]. In view of this, a completely new antenna array is designed to provide Manuscript received July 10, 2002; revised March 9, 2003. The authors are with the School of Electrical and Electronic Engineering, Nanyang Technological University, 639798 Singapore, Singapore (e-mail: ehthui@ntu.edu.sg). Digital Object Identifier 10.1109/TAP.2003.822410 an improved performance for INMARSAT-M mobile vehicles. In [4], a low-profile hemispherical helical antenna that can produce circular polarization over a wide angular range was proposed by Hui et al. Using this antenna as array elements, we designed a small hemispherical helical antenna array for mounting on INMARSAT-M mobile vehicles. With only four elements fed by a simple network, this array can produce a gain of 15 dB, a 3-dB axial ratio bandwidth of nearly 14%, a cross-polarization level of 015 dB over an angular range of 80 , a cross-polarization level of smaller than 20 dB over the half-power beamwidth, and a 020 dB sidelobe-level radiation pattern. These characteristics are better than those obtained by previously proposed INMARSAT-M antennas or antenna arrays [2], [3]. In this paper, we demonstrate a rigorous design of this array. The design is to optimize the circular polarization characteristics (the axial ratio) with respect to the interelement spacings and the relative angular displacements of the elements. II. DESIGN PROCEDURE The array is to be constructed using the central-feed hemispherical helical antenna as shown in Fig. 1(a). We denote the radius of the hemispherical helix by a and the distance of the lowest point of the helix from the ground plane by h. The angle subtended by the straight wire leading from the coaxial point to the helix with the negative y axis is denoted by . The helix consists of N turns with an equal vertical distance between adjacent turns. The equation of the hemispherical helix can be found in [4]. It was shown in [4] that a five-turn hemispherical helical antenna can produce pure circular polarization radiation over a wide angular range. A low axial ratio of 0.5 dB can be obtained at C= = 1:23, where C is the circumference of hemispherical helix and is the operating wavelength. This antenna has an extremely low profile of about 0.2 in height and a relatively high gain of about 9 dB. These characteristics make this antenna especially suitable for small-size and high-gain antenna or antenna array design for satellite communications. We design the array by using four such antennas deployed in a 2 2 2 configuration as shown in Fig. 1(b). The interelement spacings (between the centres of the elements) are denoted, respectively, by dx in the x direction and dy in the y direction. The relative angular displacements of the antenna elements are denoted, respectively, by 1 , 2 , 3 , and 4 . The design of the array is carried out by the moment method [5] aided by experimental measurements. The purpose of the design is to determine optimum interelement spacings and relative angular displacements in order to achieve a low axial ratio (AR) and a relatively high gain in the main-beam direction. Previous studies have shown that mutual coupling effect between antenna elements significantly affects the characteristics of an array [3], [6]. This is especially true for the axial ratio [3], which is sensitive to the array configuration, interelement spacings, and the orientations of the antenna elements. So we first investigate the variations of the axial ratio and the coupling effect with the interelement spacings and the relative angular displacements. A. Determination of the Interelement Spacings The variations of the array axial ratio in the normal direction (perpendicular to the ground plane) and the decoupling factor (DCF) [6] with the distance between the centres of two hemispherical helical antenna elements are shown in Fig. 2 with the relative angular displacements of the elements all set to 0 . The DCF is used to indicate the mutual coupling effect between the two antenna elements. The dimensions of the antenna elements are N = 5, C= = 1:23, and h= = 0:05. 0018-926X/04$20.00 © 2004 IEEE IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 52, NO. 1, JANUARY 2004 347 Fig. 3. Variations of the axial ratio and the DCF with the relative angular displacement of two antenna elements separated by a distance of 0.7 in the x and y directions. The antenna elements are the same as those in Fig. 2. B. Determination of the Relative Angular Displacements Fig. 1. Central-feed hemispherical helical antenna: (a) the element and (b) the array. In order for an antenna array to produce radiation with a good axial ratio, the relative excitation phases of the elements have to be aligned properly. In our design, the relative excitation phases of the elements are controlled by changing the relative angular displacements [1 , 2 , 3 , and 4 in Fig. 1(b)] of the elements. Fig. 3 shows the effect of the relative angular displacements of two elements separated by a distance of 0.7 along the x- and the y -axis on the axial ratio and the decoupling factor. The dimensions and the connection of the antennas are the same as in Fig. 2. Fig. 3 shows that the axial ratio reaches two relative minima near = 0 and 180 for both cases. The DCF shows a relative maximum at = 315 for elements separate along the x-axis and a relative maximum at = 240 for elements separated along the y -axis. But at these two relative angular displacements, the axial ratios are quite large for both cases. As a compromise, we choose the relative angular displacements to be 0 , i.e., 1 = 2 = 3 = 4 = 0 , at which a moderate DCF of 33 dB is obtained. III. ARRAY CHARACTERISTICS Fig. 2. Variations of the axial ratio and the DCF with the interelement spacings for two antenna elements with = 0 . The dimensions of the antenna elements are N = 5, C= = 1:23, and h= = 0:05. The results are obtained with element #2 being excited and element #1 being connected to a load that is a conjugate of the input impedance of the elements. Two sets of data are plotted in the figure: one for elements separated along the x-axis and the other for elements separated along the y -axis. In Fig. 2, both sets of data show that while the DCF bears a roughly monotonically increasing function with the interelement spacing dx or dy , the axial ratio does not. The axial ratio is a nonlinear function of dx or dy but we note that there is a relative minimum near dx = 0:7 (at which AR= 2:4 dB) or dy = 0:7 (at which AR= 1:8 dB). Hence we take the interelement spacings dx = dy = 0:7. An array was constructed using the interelement spacings and the relative angular displacements as determined above. The hemispherical helixes were wounded on the surfaces of four foam hemispheres, each with a diameter of 7.5 cm. The calculated and measured input impedances of a single central-feed hemispherical helical antenna are shown in Fig. 4. At the frequency of 1.575 GHz (C= = 1:24), the input impedance was measured to be 99 0 j 2 . A microstrip stub matching circuit was designed to match each element to a 50- line and the elements were excited in-phase through a one-to-four power divider. The matching circuits and the power divider were fabricated on a separate board that was driven by a single feeding cable. The matching-circuit and power-divider board was connected to the array through four equal-length coaxial cables. The size of the array ground plane is 36 2 36 cm2 . The calculated axial ratio and the power gain in the main-beam direction are shown in Fig. 5. The 3-dB axial ratio bandwidth is found to be 13.8%. The lowest axial ratio is found to be 1 dB at C= = 1:18. A very stable power gain of about 15 dB is found within this bandwidth. The calculated and measured radiation patterns of E at C= = 1:20 are shown in Fig. 6. The larger sidelobe level of the measured radiation pattern is due to the finite size of the ground plane. The copolarization and cross-polarization radiation patterns of the array at C= = 1:20 are shown in Fig. 7. Within the elevation anglular range 040 40 , the cross-polarization suppression is at 348 Fig. 4. IEEE TRANSACTIONS ON ANTENNAS AND PROPAGATION, VOL. 52, NO. 1, JANUARY 2004 Input impedance of a central-feed hemispherical helical antenna. Fig. 7. Copolarization and cross-polarization radiation patterns of the array at C= = 1:20. cross-polarization suppression is 25 dB. Hence we see that very pure circular polarization radiation can be produced within a broad angular range. These characteristics are well suited for INMARSAT-M satellite reception [1] and better than those obtained by previously proposed INMARSAT-M antenna arrays such as that in [3], which has a smaller gain (13 dB) and a much higher profile (0.675 in height). Moreover, the use of cylindrical helical antenna elements in [3] will definitely result in a small angular range of good circular polarization. IV. CONCLUSION A small and low-profile 2 2 2 hemispherical helical antenna array has been designed for INMARSAT-M mobile vehicles. Using only four elements fed by a simple network, the array can produce a gain of 15 dB, a 3-dB axial ratio bandwidth of nearly 14%, a cross-polarization level of smaller than 015 dB over an angular range of 80 , a cross-polarization level of smaller than 020 dB over the half-power beamwidth, and a radiation pattern with a 020 dB sidelobe level. These characteristics outperform those of previously proposed INMARSAT-M antennas or antenna arrays. Fig. 5. Axial ratio and the power gain of the array. REFERENCES Fig. 6. Calculated and measured radiation patterns of C= = 1:20. E of the array at least 15 dB. Within the half-power beamwidth (020 20 ), the cross-polarization suppression is more than 20 dB. The sidelobe level for copolarization reception is below 20 dB. In the normal direction, the [1] K. Fujimoto and J. R. James, Mobile Antenna Systems Handbook. Boston, MA: Artech House, 2001, ch. 9. [2] S. Ohmori, S. Miura, K. Kameyama, and H. 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